GENERAL INFORMATION

• Document Type: CREST
• Collection: General CIA Records
• Document Number (FOIA) /ESDN (CREST): CIA-RDP78-03066R000300170001-9
• Release Decision: RIPPUB
• Original Classification: S
• Document Page Count: 252
• Document Creation Date: December 22, 2016
• Document Release Date: April 12, 2012
• Sequence Number: 1
• Publication Date: January 1, 2000
• Content Type: REPORT

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50X1 -HUM
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BEST COPY 1
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THROUGHOUll
FOLDER
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Nor
SPN 2
I. GENERAL INFORMATION
1. Application
The range-only radar "Kvant" is designed for installation, togetier
sight ASP-SN or ASP-SND and permissible range computer VRD-2A, on jet fighL,?:
The range-only radar ensures automatic and continuous determinat,on
distance to the target and of relative rate of approach to the target
The range radar "Kvant" operates in two modes:
"Mode A" -- firing is done from guns or with unguided rocket project_ 31s.
The range finder feeds continuously to the sight computer voltage pro)ort,(,:aL
to the target gange and relative speed of the target.
"Mode B" -- launching of class air-to-air homing missiles '-13.
For this mode the range radar ensures:
a/ Determination of present /ange to the target and displaving a au Ii
information on the pilot's firing-range indicator UD-l.
bj. Automatic comparison of present range with permissible range of K-:
rocket and providing launching permission signal.
vifSignalizing the approach of withdrawal-from-attack rnj
2. Basic Tactical-Technical Data
a. The range radar "Kvant" determines the distance to aircraft -tart
in following ranges: from 300 to 3,000 meters for mode "e and from -600 ii
7,000 meters for mode "B"
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b. The range radar feeds automatically voltage proportional to the
distance to the target to the type ASP-SN sight computer (mocle "A') 01
to the pointer range indicator "UD-1" (mode "B").
V. Range error does not exceed ?15 in for mode "A" and ?100 m ftr
g. Range radar determines the rate of approach to the aircraft.Gar
(relative speed of the target) in a range from +400 m/sec to -.1?)., /s.,:c, Lod
automatically feeds to the sight computer ( mode "A" ) or to pea= r
range calculator (mode "E") a voltage proportional to relative velocity.
speed, when closing in on the target, is positive.
d. The error of speed determination does not exceed ? 15 Al/sec for
mode "A" and ? 85 m/sec for mode "B".
e. The range radar de'Germines the instant for launching rocket K-13
? by comparing present-range voltage with permissible-rocket launching ranal
voltage admitted from permtssible range calculator VRD-2A.
zh. Range resolution of range-only radar is not less than 200 it. ir 41
z. Dead zone of the radar is not greater than 300 in.
i. Directivity pattern of range-only radar at half-power in botu plaie5
is equal to 18? + 10 (or -20) for mode "A" and 60 ? 40' for mode "B".
k. "Pulse power is 5 to 7 kw.
L. Duration of high-frequency pulse is 0.5 ? 0.05 microsec.
in. Operating frequency 9370 ? -5 Mb.
n. Pulse repetition rate 800 ? 100 pps.
o. Sensitivity of receiver circuit (mode "A") is 87 db for a raige
r
2000 in and 68 db for a range of 500 in with reference to 1 millivatt.
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13?
Pull-aut from attack range is 1000 to 1150 m.
? r. Ceiling of the range-only radar - 25000 m.
s. Power consumption of range radar from 115 v, 400 cps power .lime 1
410 va; power consumption in +27v circuit is 25 w when ambient temetatuil
is above 0?C and 130 w when temperature is below 0?C.
t. Weight of the range radar without intermediate cabJes is 30 --A.
u. The range radar can operate, continuously for 6 hrs.
f. Guaranteed service life of range radar is 500 actual flight lour.
SPN 5 on an aircraft during a period of 3 years, if all regulation inspections
and maintenance work is observed in accordance with operational 11181111S,.
3. Range Radar Assembly
The assembly of the range radar "Kvant" designed ror aircraZt
comprises the following units:
a. Combilid antenna with waveguide line - GYa 2.060.05L. Sp
b. Receiving-transmitting unit RB6-21,4 GYa 2.000.024 Sp - oiecF-
v. Range-only radar receiver unit RB6-3 GYa 2.003.002 Sp -i picce
g. Power pack unit EB-6-4 GYa 2.087.004 Sp - 1 piece
d. Speed indicator unit RB-6-5 GYa 2.002.005 Sp - 1 piece
e. Control panel K-6 GYa 2.761.031 Sp - 1 piece
zln. Comparator unit K-8 GYa 2.08.012 Sp - 1 piece
z. Intermediate cable ITpl-F/Gra 4.853.165 Sp - 1 piece
i. Coaxial cable GYa.F.850.135 Sp - 2 pieces
k. Control mechanism Klic GYa 2.781.037 Sp - 1 piece
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, Speed calibrator for 5 assemblies, type "KS-2" GYa 2.761.021.8n and
control instrutent KPK GYa 2.761.0378p are part of the special control-tel-
p, equipment of the range radar "Kvant."
II. PRINCIPLE OF OPERATION AND
INTERACTION OF INDIVIDUAL
COMPONENTS OF RANGE RADAR "KVANT"
1. Principle of Operation
The principle of range radar operation is based onilluminationof a
given space zone by short-duration recurring electromagnetic pulses, and
reception of such pulses after reflection from a target located in the zalJt
of :111uMination.
?The range radar "Kvant" determines the distance to the target by aut-
matic measurement of time interval between the initiation of probing 7also
and the instant of arrival of pulse reflected from the target, _ fig. 2.
The range radar "Kvaut" is an automatic electronic device which does
not require attendance, except, for switching-on during take-off and Evritchz_i
? off during landing.
? Observation of range radar "Kvant" performance in flight can be Awn__
out by watching an aircraft-target flying in front; after target Iock-on
the radar, a green lamp "lock-on" lights on the sight head.
For mode "A" operation the manual feed of range to the sight is tlisc.c-
nected'at this time (handle of gas sector), and the size of outer circle
the vision and target field is now changed only from the range radar.
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For the mode "B", the firing sight is set into position "fixed" nrWx f
at this time the illuminated mark occupies a position corresponding to di:
tion of aircraft tun axis, and the pointer indicator UD-1 on the instinnet:
board snow automatically the distance between the aircrafts.
Thus, aiming is done at a stationary mark, as on a collimatcr siftt.
SPN 9 Relationship between the distance to the target, the velocity of &let-
NW'
tromagnetic wave propagation in free space and the time interval from the
moment of sending high-frequency probing pulse to the instant oi receatior
of pulse reflected from the target is defined by the formula
t= 2D
where: t - timP interval for high-frequency pulse to travel to the tixget
and back; 2D - doubled distance to the target, i.e., distance to target at
back; S - velocity of electramagrotic wave propagation, which is equa:1 to
the speed of light
S = 3 x 108 Oec
Time measurement is carried out by continuous superposition of tLe tet.-1!
pulse on the selector pulse, which is generated by the range finief. _ctr
time of selector pulse is related linearly to voltage applied, to the ejrcuZ,
of time modulator, which generates such pulse, i.e.,
= Kl (Uo-Ue)
where: tz - delay time. of selector pulse
UD - control voltage
Uo - initial voltage
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IOW
Due to coincidence of the target pulse and selector pulse,
2D
or Up= U0 - = U0 - KzD
tz=t, and KI(Uo-UD) =
Thus the voltage controlling the time modulator becomes proportional
to the target range. This voltage is fed by the range radar to the s ght
computer and to indicator UD-1.
The selector pulse consists actually of two pulses, generally ca?led
range pulses (see fig. 3). These 0.7 microsec duration pulses, shifted 0 1
microsec with respect to each other, conduct search-scan in absence o
fleeted pulses, i.e., they are shifted along the whole range of cListances
from 200 in to 3000 in with a frequency of 1 cps (mode "A") ani from 800 in -(
7500 in. with the same frequency of scan for mode "B".
The shifting takes place from shorter range toward longer. In the
event of appearance of a pulse reflected from the target, it comes ino cc.
incidence with the range pulse. At this time the lock-on circuit goer;in
operation and the search-scan is discontinued. The range radar locks on -1
target and begins to range-track the target by feeding voltage propor-doni:
to the range to the sight computer or to the pointer indicator UD-1.
The range radar "Kvant," in addition to range voltage, also supp. les
voltage proportional to the relative speed of target.
The speed voltage is obtained by differentiating range voltage lei ill
subsequent amplification by a special amplifier located in the speed 1,n-it.
The law, for range voltage generation:
For MOde "A" -- = 195
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Nori
For mode "B" - UD = 195- D
50
where: Up is voltage in volts
D is range in meterc
The law for speed voltage generation:
for mode "A"-- Usk = - 0.1V
for mode -"B"--- Usk = - 0.04V
where: Usk - voltage in volts
V - speed in meters per sec.
For an approach the speed is positive.
The peculiarity of the range radar "Kvant" is its ability to operate
in two different modes. For this reason the radar antenna consi.sts t-by)
different antennas - of a horn antenna producing a vide 180 + 1? or -2?
beam for mode "A") and a reflector antenna producing a narrow 60 k 40' beie
for mode "B".
A switch located in the range radar connects one of the antennas to
receiver-transmitter unit.
The antenna switching is controlled from the aircraft circuit.
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SPN
13
5. Blocl Diagram of Range Radar
As Seem from fig. 4, the range radar "Kvant" consists cf antenna uni
receiving-transmitting unit,. range-only radar receiver, power supply.unit,
speed unit, Control board. comparator unit, intermediate cable and. COAXiet
cable.
Antenna Assembly Unit - consists of a combination of a horn antenna
with dielectric lens and a reflector antenna with horn exiter.
This antenna assembly is designed for highly-directive radiation of
high-frequency electromagnetic energy and for reception of aigna3s reciectl '
from a target.
Directivity pattern of the horn antenna while in mode "A" is 18? 1
or -20 in both plAnes.
Directivity pattern (or beam width) of reflector antenna while ir
mode "B" is 60 ? 40' in both planes.
The receiving-transmitting unit forms and radiates powerful high--Precl-n:.!r
pulses automatically adjusts frequency of local oscillator, recives and
amplifies reflected signals; switches antenna from transmission to rec.:3pti,
and synchronizes the work of range-only .receiver unit.
The receiving-transmitting unit consists of a high-frequenc:!, f * 937)
? 45 Mc, magnetron oscillator, a modulator, a sub-modulator, kly3ron loca
oscillator, receiving-tranamftting chamber with mixer, APR tube, -Ipark-gap
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%NO
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discharger, mixing chamber for automatic frequency control (APC11), Irean:
fier of intermediate frequancy IPUPChl, AFC circuit, high-lroltage rei-bift
and pre-ionization rectifier with ignition current stabilizer.
SPN The range-only radar receiver unit serves to amplify the IF of ,lefl! ,t
14
pulses, to detect such pulses and to convert them into tarFet NrLdeo-ouls
, to fix the time of arrival of reflected pulses and to form voltage to the the distance to the target.
Power supply unit 'provides stabilized voltage to all unit-1 of tle
radar. The unit contains a rectifier for +150 v and +200 v, a recti ler
+300 v, a rectifier -150 v, electronic voltage regulator and a reference
stabilovolt.
Speed indicator unit serves to determine automatically the rala ive
speed of target, and to supply appropriate voltage to the firing sigkt arc
permissfble range computer VRD-2A.
Control board serves to facilitate the operation of the range-oro_v re Its
installed on an aircraft. All controls of the range radnr and the centro
points for checking the performance of the automatic lock-on are located )
Comparator unit serves to convert the voltage scale of tar -!b
range into a scale corresponOing to the scale calibration of the UD-1 pott
range indicator, to compare automatically the voltage of target _-)resent rl
with the voltage of permissible launching range of the rocket, and to sell
launching permissible sial to the green lamp "launch" installed on -he
pilot's instrument board, to 'determine the moment for withdrawaL from attur
by sending a signal to the red lamp "-pull out" installed on tYe pilott?
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OUA I -riuivi
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NI/
Intermediate Gable Wiring Diagram
(1) Sh-8
Flu Rit?PK175Sh1
FunctionFern.
No.
2
3
ground
4- 115 v (corn)
115 v (corn)
+ 27 v
5
Urange unit
speed scale
+ 200 v
lock-on circ.
speed zero
speed zero
tracking
Uspeed
lock-on sig I 13
6
7
8
9
10
11
12
- 150 v
15
16
17
+ 300 v
+ 150 v
(2) Sh-3
Plug R48PKESh1
Goes Function
too.
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ground
+ 27 v in.
+ 27 v out.
115 v in. (corn)
115 v out. (corn)5
115 v in.
1.15 v out.
'7
search freq.
4-D search freq.
1 4. 150 v out.
4. 15o v in.
o + 200 v
Urange A
range zero
range scale
speed scale
speed zero
speed zero
ferrite switch
Urange (input)
150 v
9
10
LI
12
13
lit
15
16
17
18
19
20
21
22
Urange
sensitivity 23
AFC circuit 24
ferrite 341. eryst.25
mode signal 26
ferrite switch 27
ferrite switch : 28
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Sh-7
Socket R4811K28EG1
Goes:, Function Term.
to' 4o.
1
2
3
4
LO
11
12
13
1)4
15
16
17
18
19
to External Circuit
ground
altitude sig,
+ 27 v in.
115 v
4a, 115 v (corn)
input switch
input switch
? input SW.
? input SW.
lock-on sig.
mode signal
VRD supply
VRD supply
VRD output
range instru.
range instru.
Uspeed
pullout sig. 20
+ 200 v 21
A 22
range
clearing
- 150 v
launch sig.
23
25
altitude sig.J 28
(4)
Sh-5
Socket 2RM2)0(PN19G1A1
Goes
to
Function
Terr,
No.
ground
A. 115 v
^0115v
uspeed
4 27 v
1
2
3
ferrite SW.
crTS
6
Urange
7
Tk I
Tk II
TM
10
+ 150 v
launch
12
- 150 v
13
meas. ground
, 14
+ 200 v
' 15
z
+ 300 v
. 16
RRCh (MFC)
, 17
0
4-,
RRU (MGC)
18
calibration
19
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SPN 15
(5) Sh-2
Socket RG40U17EShl.
Function
ground
A? 115 V
eNd 115 V
+ 27 v
meas. ground
+ 150 v
Tk I
erm.
40.
1
2
(corn) 1 3
4
5
6
7
8
9
,v 115 v in. 110
11
- 150 v 12
APCh (AFC) amp 13
RRCh (MFC) 14
TM 15
Tk I 16
+ 300 v 117
( c)
16
;F:a37i7T
(6) Sh-1
Socket 248PK28iShl
Function
Goes
to
to Unit No.
ground
+ 27 v
115 v
N 115 v
+ 300 v
i? 200 v
? 150 v
- 150 v
Urange
tracking
range scale
search freq.
search freq.
UPCh (AFC) 3hift
lock-on circ.
sensitivity
launch pulse
+ 150 v in.
clearing
range zero
orange' anit
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Nor-
SPN 15
(7)
Sh-4
Socket 2R430BL132G1A1
Goes uric ion Term.
to
ground .1
+ 27 v
+ 300 v 3
4 200v
+ 150 v
supply 6
supply 7
VRD output 3
in. 9
urange
instru. "D" 10
instru. "D" 11
12
uspeed
pullout sig.
launch sig.
13
lh
15
16
mode signal 17
18
lock-on circ. 19
20
21
altitude sig. 22
altitude sig. '.23
24
25
26
27
28
29
calibration 30
? 115 v 31
A1 115 V (COM) 32
- 150
(8) Sh-6
Socket 2R/4141PY4G1A1
Function TTrrn.
Eo.
Goes
to
to Unit No. 1
ferrite switch
ferrite switch
ferrite switch
(d) - 17 -
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1.0("1 -I-1U IVI
? SPN
16 ,
Igor
SPN
18
instrument panel, supplying +28 v stabilized voltage with res t ,
voltage, to VRD-2A.
Intermediate cable serves to interconAect the units of the rang?on:
radar on an aircraft. Cable configuration and size depends on the dt,p1o1r4.-1
of the range/finder on a given aircraft. Schematic lay-out of the iLternE
ate cable for the MIG-21F combat jet is shown in fig. 5.
6. Functional Diagram
On fig. 6 is shown the functional diagram of the range-onl/ radE-
"Kvant". This diagram shows interaction of individual components of the
range radar.
The operational mode of the range radar is different for the seco..ch_.
'scan of the target from the tracking of target, when the reflected 34- al
enters the receiver input.
For this reason the description of functional diagram is divided int,
2 sections:
a/ Search-scan mode
b/ Tracking mode
Search-Scan Mode
The submodulator located in the receiving-transmitting unit genelatef
positive voltage pulses with amplitude not less than 150 v, pulse duratior
of about 1 microsec and repetition rate of 800 pps. These pulses control
the discharge tube of the matulator.
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ra
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180 v VRD-2Arilgnal
7
AnteniitIFerrite 4Antannar'Time Compaictor
oammutatorwewitch "Modulator Circuit Circuit
pill-,.ht , 4 . T. ludioat,ok
i
aigna1 UD4
^
-VttrAUT7
I
1 0.5 miceec range pulse
_ . error
rIF ' Detect() Video time current IspeWa-Giputing
ampl. 2 1. rv1scrdadnato- ontrol Unit ------>Circuit
2-nd integrate
;Opera .
Amplifier
T.
35 to 1951v
Lock-on
Circuit
-Haw
High-volt. ;Sub- i0L---41 AFC
Rectifier , [1,!odulatoril Mixer
+200v -150v
+300v +150v4%
id
1 Power
Unit
7/14
Fig 6. Functional Diagram of Range-Only Radar nvantit.Uc
-t OtYvi 1-4c-A -?3,1 kLkr
ci:Lirtak
0
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The modulating pulses with 5.5 lor amplitude, 0.6 microsec durat:on
repetition rate of 800 pps are generated in modulator and are fed to the
magnetron.
Magnetron oscillator generates pulses of T 0.5 microsec durat.on nui
power of not less than 5 kw.
The antenna switch disconnects the receiver during the action oa' prct
pulse.
Powerful high-frequency magnetron pulses are admitted through ht.gh.-
frequency channel to ferrite commutator which directs the electromagleatii:
energy to one of the antennas, depending on the operating mode of ratige-un
radar.
Part of high-frequency energy of the magnetron pulse 13 admitte to
mixing chamber of A.F. Undamped high-frequency oscillations from klstrcz
local oscillator are also continuously admitted to AFC chamber.
As a result of mixing of two high-frequency oscillations, a pale ii
formed at the AFC output with a frequency which is equal to the difference
between the klystron and :magnetron frequencies.
This pulse is converted by the AFC circuit into the control voltage, 191
which .is fed to the klystron local oscillator and maintains klystron frec.41,:,,neT
above that of the magnetron frequency by a value equal to IF.
Simultaneously with tne modulating pulse, a negative synchronizing
is fed from modulator to:
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a) to IF amplifier and disconnects receiver during the transmL;siol 1V
main probing pulse;
b) to noise AGC and euts it out for the reception period-, thus- el
ing the effect of target pulses on performance of :the,meide ALIC:
v) to fast saw-tooth forming circuit and triggers it.
The !!fast saw-tooth" circuit feeds to the comparator circuit =It RV
-
a saw-tooth pulses at a rate of 800 pps and of 25 or 50 microsec duretior
(depending on.the mode) and of 150 v amplitude .(fig. 7).
In addition.?to the comparator =malt unit RB6-3 is fed a saw-teoth
Voltage from the "slow saw-tooth" generator, which varies in intensity fr1,-,
185 to 20 v during a period of .8 to 1.2 sec.
With this gradual decrease of "slow saw-tooth" generator voltage, th-i
occurs greater id greater delay in conduction of comparator diode f.7)r-ea,!!
successive period of 800 ppc repetition rate.
Thus, to the subsequent circuits of the Comparator is almitted a saw-
tooth pulse with leading edie lagging more and more behind the '-.1-9n,511- tte
pulse as the sweep generator voltage decreases.
SPN This pulse is amplified and differentiated, and is used to trigr rrx
20
pulse generator. The latter generates 100-v range pulse of .7 micro c d419-
tion which is fed to time disriminator. Tne time discrimina;or operaCas cr
during coincidence in timp of range and target pulses.
As is seen from Jig. 7, with gradual decrease in voltage of the ',11o.t.
saw-tooth", the range pulses traverse the whole working range of search-
scanning at a rate of .8 to 1.2 cps.
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OUA I -riuivi
The noise voltage fro receiver output is admitted to noise AVC hirvu
which develops negative vuliage proportional to noise magnitude. Thi_s
age is admitted to IF amplifier, and. by varying amplification factor he it
level is maintained constant at the receiver output.
Tracking Mode
Pulses reflected from the target are intercepted by one of the pnterA-
depending on the mode of operation,and are admitted by high-freluency chsi
through the ferrite switch to the antenna switch, which prevents the ent'
of reflected signal to the magnetron circuit, but admits reflected 0013e8 o
the mixing chamber of the receiver.
At the mixing chamber of the receiver the reflected sinal 'rehuncy
mixed with the local klfs-aron oscillator frequency.
SFU As a result of mixing,a number of frequencies are formed from whch
21
30 mc IF is separated out at the receiver mixer. Input circuit of IP orey4--
plifier (PUPCh) serves as the load of the receiver mixer
After passing through the IF preamplifier; the signal reflected f-om
target is admitted to the main IF amplifier. The target signal after sec(ui
detection and amplification in IF amplifier is admitted to the input ( 7
discriminatorthraugh the video amplifier and cathode follower.
Time discriminator fortis error current at the instant o' coincidence -
the target reflected pulse with the range pulse. Such error-current ta.lue
depends on magnitude and sign of mismatch between range and tarTet pu.(es.
The error signal is admitted to the input control-unit circuit, which s IH
the form of a double integrator.
? 23 ?
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Nor'
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50X1-HUM
The time discriminator ml so generates negative pulses which control
the automatic lock-on.
At this time the automatic lock-on goes into operation am.: search-set,
generator circuit is transformed into a double integrator and the sinal
lamp "lock-on" lights up on the sight.
The range-only radar circuit now switches to tracking mode and -.)roc-
esses VOltages:Proportional to the target range and relative speei. of the
target. At the instant of target lock-on and switch-over of "slow sew-torli''
generator, at the output' of doubie integrator remains a voltage (2orresoothi
to target range, as it was at the instant the automatic lock-on went into
action. This voltage is fed to the comparator unit circuit I336-3, it.ei 23]
of the "slow saw-tooth" generator voltage, and it controls the 'ange-rulso
displacement in time.
The error current of time discriminator is continuously adlatted to -
double integrator until the range pulse comes into balance with the targe-
With the disappearance of target signal, the autamatic loci: -on i3 re
leased after a delay of 1 to 1.5 sec.
, The output range voltage continues to change accordingly with the selLe
law and at the same speed during the delay period as it occurrea prior to
target disappearance, thus ensuring the "memory" of target speeu.
Pulse from theplateafautomatic lock-on amplifier is fed to input of
AVC circuit. This pulse is amplified and detected, and as a negative de -tc:
age is fed to IF amplifier, thus changing the receiver ampli2ication thick' q
necessary to avoid overloading receiver stages and to decrease the raroe
for targets of different intensity.
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Noir
The performance of noiise AVC in both search-scan and trachL,
identical. Pulse AVC and n6ise AVC have common output to IF
es
through cathode follower. &len range-only radar "Kvant" locYs-on t.arg-t
in mode "B", the range voltage is fed to electronic circuit in unit - 3
which compares it with permissible range voltage, the latter calving t- u
computer VRD-2A.
By permissible range -Pcm rocket launching is understood a maximl
tance to the target at -which the rocket will necessarily reach the ta:get
while the homing system f_s in operation.
Such a range is defined by the following equation:
(K) ,
Drkm = 3.06 ? 10-3 A Vsr (Val) + D j
The magnitude of permissible range depends on the aircraft altitude
air speed of aircraft-Carrier (VA), as well as of magnitude and Agri
of relative speed (D).
Permissible range becomes greater with the increase in flight al-Attie
(air resistance becomes smaller), with the increase in speed of the carTie:-
(initial speed of rocket), and with increase in relative speed o ' app-oach
to the target.
The permissible range computer 1TRD-2A consists of a potentiometr c
transducer, which is fed with dc voltage from range radar, and which rop
a voltage proportional to permissible range according to the fo _Wing JA4,-
Ut-razr iv! = 3.625 (Drasr in km )
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I P 2141
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The VRD-2A solves the equation:
Vsr LN )
and the obtained 'voltage is added to the relative speed voltage vhici
was admitted to range radar "Kvant" according to the following :aw:
Ud (v) =
Uf is positive during approach.
Speed range: from -100 Al sec to +400 m sec, which corresponds t(
voltage variation fran -4 v to +16 v.'.
Total voltage from the slider of VRD-2A potentiometer is admittec to
electronic circuit oftle-can.parsteruittIC-8. When the present range to targe.;
becomes equal or smaller than the rocket-launching permissib Le range thai.
the comparator circuit operates and on the pilot's instrument board lighte
on the green lamp "launch." From this instant the pilot may launch the K.:
rocket if all other required conditions are fulfilled.
Present range voltage is also admitted to a special circuit whia,, 111.4-,1
approaching a range of 1000 in, lights on a red signal lamp ":pulD-out,' th7o: ,
warning the pilot of the danger from further approach to the target. Sucll
further approach may result in collision with the target or damage from tl
fragments of. the rocket.
On the pilot's instrument board is located the pointer indicator- UD-1
range to the target, which is in the form of a voltmeter graduated di-
rectly in km, from 0 to 8 km. This range indicator is fed with power thrctl.
operational amplifier of K-8 unit.
S-E-C-R-E-T
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THE ANTENNA WM:GUIDE ASSEMBLY
7. Application
The antenna -.14tevegaide unit is designed for transmitting high..-
frequency power from the -oscillator to the antenna, the radiation r
/ .
this energy Into space within the limits of definate spatial angle thh
reception of signals reflected from the target and their trans ission
the receiver.
8. The basic tactical-technical data of the antenna wavailuide cha
1. The width of the directivity pattern in the wide beai modelmodl
is 18 + 10 in planes E and 11, and is 6? + 40 in the narrow bea
- 20
mode/mode "B"/ Lb, both pines.
2. The side lobes do not exceed 5$ of the maximum in both mods.
!WV
3. The gain factor of the antenna is equal to 85 in mode "A" nd
550 in mode "B".
4. The standing wave ratio of the antenna -vravegnide un Lt doe 7 not
exceed 1.5 at frequency runge. of 9370+45 MC.
The antenna-waveggia0 unit of the "KVANT" range-finding 1.adar con-
'sists of two :structurally combined antennas and a wavegmide (!hrine't T
a ferrite commutator, which provides for switching the operating maes -
the station/wide and narrow beam/.
The gain factor is determined by comparing the antenna :.P 271
being tested with the standard one, the gain factor of which is knom -i.
the following formula.
G isprx G et x i-142
111111.1 S-E-C-R-E-T
50X1-HUM
, where
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G isp is gain factor of the antenna being tested.
G et is the gain factor of the standard antenna.
P isp is the power being received by the antenna being tested.
P et is the power being received by the standard antenna.
The gain factor of the antenna for the "KVANT" range Cinding ndar
is equal to 85 in the wide beam /mede "A"/ and 550 in the narrow.beLm
/mode "B"/.
For a more complete transmission of the transmitter power to tte
antenna, matching of all the high frequency channels is of great im,'porterc:c
The matching of the high frequency channel is characterized by the *a.:1,1*
of the standing-wave ratio.
In an ideal case, during the absence reflection, a traveling-lvve
mode is established in the high-frequency channel /during whi(M swa-1
In the. presence of reflection a standing Wave appears in the chariel.ii
Such standing wave is formal as a result of the composition oZ incient
and reflected waves.
The standing wave ratio is defined as the ratio of the maxium:
value of voltage in the line to the minimum
U
KSB (swil) max C.
Ti min
the better the matching, the smaller the difference between U maximilm arm
U minimum
, and consequently the smaller the magnitude of 31.tt.
The standing wave ratio in the antenna-waveguide unit of the "WAri- .1? 28]
range-finding radar does not exceed 1.5 in both modes.
The wide directivety pattern of the "KVANT" range finding rada-
S-E-C-R-E-T
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NOW
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"At/is radiated by the horn antenna. The directivity pattem of the hors
antenna depends. on the dimensions of the horn, its length and size Of the
aperture of the output opening.
In the horn antenna a dielectric lens is intalled in he aper reci
the horn. The dielectric lens serves to equalize the field phase in the
horn aperture, which; in turn, leads to higher gain factor and lower inten-
sity of the siae lobes of the directivity pattern. The side lobes are re-
sponsible for useless diffusion of a part of the radiated power and or
ering the noiseproof feature of the station. The electrica_i_ field oi the
horn has vertical polarization. The horn antenna is connected to the wave--
guide through a coupling transformer with a 12 x 23 mm cross section, and
tuned in designated range of frequencies with the aid of a matching stub.
The air-tightness of the antenna is achieved with the aid of ptly-
styrole foam bushing, which is pastet, to the mouth of the horn with epoxy
resin.
The narrow directivity pattern /mode "B"/of the "KVOTn range
radar is radiated by the reflector antenna.
The reflector antenna is a radiating device in which the eiectro-
magnetic waves from the primary exciter is directed by the reflector into
space within the limits Of -a certain space angle, depending on the cliemeta::
of the reflector.
The antenna reflector is a circular parabola with a diameter of 360 m
and a focal distance of 235 rim.. The focal distance was selected in sach a
manner that the primary radiating element of the reflector antenna
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50X1-HUM
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would in a least degree overshadow the radiation from the horn antellaa
located behind the reflector /fig. By.
The primary exciter of the antenna is a horn radiator. The si4..e el
the horn radiator ?-,is selected in such a manner that the radiat5en af_rec-
tivety pattern formed by it would have in the direction of the edge
reflector; considering the spatial attenuation, an intensity
times of the maximum power, thus the power density at the edge
parabolloid becomes 6 to 10 times smaller than at its central part.
Under such a condition, the optimum value of the reflecto sur race
utilization ratio, which is necessary for obtaining the maximula gaio
factor of the antenna for n given diameter of the reflector, is rovLden.
The polarization of the electrical field of the antenna is horizontal-
The horn exciter is off the focus by 60. This makes it eossihe,
firstly, to reduce the effect of the reflector surface on matching tle
waveguide channel and, secondly, to remove the exciter of the refleoLor
antenna from the radiation gone of the horn antenna.
Since part of the energy of the horn strikes the exciter, is teflecoa
from it, and during the second reflection from the reflector it narrows
radiation directivety pattern of the horn antenna, Ametal grid math of?
vertically arranged wires is installed in the aperture of the 'eorr
/fig. 8/.
Such a grid is transparent :ttf the electrical field with noril.ontzi -
polarization,since the vector of tho electrical field is perpendicu:ar
to the direction of the wires. For the electrical field with vertical
polarization, the vector of the electrical field is parallel to the
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P 30]
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VOW
. direction of the wires, consequently, for such a field tha grid is equit-
lent to a metal screen which completayreflects the electromagnetic fielc:
The grid in the aperture of the exciter ie located In Bach almoner that ti,
energy of the horn antenna, the electrical field of which has vertical oolr
'A.ion, will be dispersed by reflection from the?grid.
The wires of the metal grid of the exciter are fastened to a
made of foam polystyrole. The bushing is pasted to the mouth of ihr hote
exciter with epoxy resin, thus forming air-tightness Of tiv: high-frernterc -
channel.
The horn and reflector antenna are fastened to a common mounting .-b,7
a cast magnesium alloy braaet,while the horn antenna is locatad behind '
the central part of the reflector antenna. For this reason, later
made in the form of a metal grid with horizontal wires which mans it tr
parent to the energy radiated by the horn antenna.
The combined antenna- is fastened to the airplane with the aid ').1?
four bolts, which are mounted from the side of the reflector, througl
special hole to a cast bracket and auxiliary fasteners, provided on '":,he
airplane.
9. Waveguide Channel
Block diagram of waveguide channel is shown on fig. 9.
The waveguide channel is built with rectangular aluminum wave lile
of 23 x 10 mm cross sectior, except for ferrite commutator.
High-frequency admitted to the waveguide channel from receivi
mitting unit (unit aB6-20 is fed to the ferrite commutator, which it
turn directs it into one of the antennas depending on mode of radar r7lerat.
50X1-HUM
321
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10. Description of Ferrite Commutator
The ferrite commutator switches.on the two antennas a1tg7-ratey,
radiating different directivity patterns.
The polarization plane rotator and a tee' form part of t14 oo utelJ
(fig. 10).
Ferrite commutator operation is based aatheirtadple of nolariat
plane rotation .
The ferrite stub, located in transverse magnetic field, rotatea
polarization plane of electromagnetic wave that passes through it.,
Ferrite polarization-plane .rotator is in the form of a sguare,
21 x 21 mm waveguide section, inside of which in a fluoroplastio insert
mounted grade M-77 ferrite stub of the following size:
d=6.7 i 1=70 mm
Electromagnet winding of 5,000 turns from .2mm PEV wire is plAged
outside the square waveguide.
w=5,000 turns
One end of the square waveguide polarization rotator is ter in'
by a quarter-wave transformer, which is needed for.transition f-o
waveguide to 23 x 10 mm waveguide.
To the other end of the polarization rotator is connecteC
outlets of which make 900 'Kith each other (see fig. 10)
For mode "A", a current of the order of 50 minim* )asses throng)
electromagnet winding. Such current ensures polarization-plane rotatIon
by 900, i.e., the passage of electromagnetic energy to channel Ti.
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1) 341
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For mode "B" a cur-:.ent of the order of 5 milliamp, need t?, reve
residual magnetism, is pasf;ed through the electromagnet wiITdin. Su-h
residual magnetism originates in the ferrite stub during -operation i no
ItA ti
Now the electromagnetic energy is directed into charnel U. Carr ii
direction in the ferrite-cummutator winding in mode "B" is opposite -o
that for mode "A".
SPN 36 Electromagnet current switching is effected by A6-3 relay. loc ted
in unit K-6 which is actuuted by the mode signal. To ensure oieraton
at high altitude, the waveguide channel is made tight with the iid o
rubber gasgets.
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k 3,04
.are
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IV. BEC3IVI1G-TRANS4IlliNG UNIT
Applicatidn
The RB6-2M receiving-transmitting
unit goes into the makeup of tt... fP 361
"NVANT" airplane radar ran finder and is designed for gene:ating poverful
high frequency pulses, switching of the antenna from transmission to rece-
tion, reception of the signals reflected from the target awl their preamri
fication.
In addition, the receiving-transmitting unit performs automatic
frequency control of the local oscillator and generates pulEes, which syn-
chronize the operation of the entire station.
12. Make uE of the unit
The 'receiving trarumitting unit consists of the follow .ufY,
a) submodulatcr;
b) Modulator;
v) magnetron oscillator;
g) antenna switch;
d) mixer of the receiver;
e) mixer for the Alrh (automatic frequency control);
zh) klystron oscillator;
z) preamplifier for intermediate frequency PUPCh/;
i) high-voltage rettifier;
k) rectifier for the pre-ionizer;
1) systems for automatic frequency control Of the k_ystron orci
tor /APT*
p-E-C-R-E-T
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i71
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13. The basic tactical-technical data of the unit
The receiving-trwaamitting Aullt has the following hasjc pan, ti.!
) pulse power of high frequency oscillations
imp 5 kw
b) the fre uency cf high frequency oscillations in a rang
)570 ? 45 Mc
v) duration of mOulating pulse
T imp. = 0.5 ? 0.05 microsec
g) the band width of high frequency oscillations at the
X s' 6 MC
base
d) pulse rePetitior rate
Fn = 800 100 pps
e) Synchronization-pulse amplitude is not less than 80 7.
zh) The average current of the magnetron is equal to + 0;7 (.?
z) The crystal current of the receiver channel is 0.2 to0.8T4)3Pt
i) The crystal current of the AFCh (AFC) channel is 0.4 41)2.'
k) The ignitor firing current of the ATR tube is 70to9!-,, ic.y.oamT
1) The average intermediate frequency PUBCh is 30 ? 0. Me-
m) Overall dimensions of the unit are:
D = 240 mm
L = 388 mm
n) the weight of the unit does not exceed 12.1 kg.
o) The unit opera4;e13 normally:
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fl
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a/ during a temperature change of the surrounding atmosphere frol
4- 50 C to -60 G.
b/ after remaining 48 hours in an atmosrbere with a relative humi_ -
ity of 95-58% at a temperature of 205?C.
v/ "at altitude of up to 25,000 meters, [that is at an atmosp xeri
pressure of up tc 18.6 mm Hg.]
14. Description of Unit Operation
According to the FUnctional Diagram
[Fig. 11)
Blocking oscillator of the submodulator utilizes the left --laDf
L2-3(6NIP) dual triode; 1 generates potive voltage pulses o? 2 0 vmpi
tude and 5 to 8 picrosec duration with repetition rate of 800 pos. These
pulses passing through the cathode followerxwhich utilizes the -'ght Leif
the dualtriode 12-3(6MP), controltteperformanceof the modulator disc1ar7e in
Pulses from the blocking oscillator 1.2-3 are also admitted thrau4h lit,
cathode follower 12-4(6N3P) to the AFC system, where they are used fOomegl 1-
ulation (modulation) of the screen grid of the pentode L2-18(6NID).
The modulating pulses of 5.5 kv amplitude, 0.65 microsec turati:n1c1-
repetition rate 800 pps are formed in the modulator dasedbled as
circuit with artificial pulse shaping line and hydrogen thyrotron L2-1
(TGI-1-35-3), the latter acting as a discharger, and axe then fed to the megtaa-1:xem
1.2-9 (MI-158)
Magnetron oscillator gpnerates pulses of 0.5 microsec dura?cn aid '.)9]
not less than 5 kw power.
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Powerful high-fretuencl pulses from magnetron oscillator are adrAte'
to antenna and are then irradiated into apace. Due to the presence cr an-
tenna switch in form of a RR-21(12-12) ATR tube, the receiver hecomer dis-
connected during the transitission of main pulse.
Negative synchronizing pulse with amplitude of 80 v is also taken fr
the modulator which is fed to IF amplifier for disconnecting the receiver
during transmission of main pulse, for disconnecting the noise AVC cireui
during reception and for triggering "fast saw-tooth" multivibrar loatei
in the range unit.
Part of the energy of the high-frequency pulse from the magnetral osA7 -
lator is admitted through attenuator to the mixing chamber of .,VC, where =
crystal detector D2-1(D2-2) acts as a mixer. To the AFC mixing chamber a:1,
also admitted continuously high-frequency oscillations from klystron sci.-
lator 12-11(K-27).
As a result of mixing of two high-frequency oscillations, at the autpu:
of the AFC is formed a pulse having a frequency equal to the differeuce 14.-
tween the frequency of klystron local oscillator and the frequency cfinagrf
tron oscillator.
This pulse is amplified by two IF stages of the AFC circuit assenhle
with diodes (I2-17,L2-18), and is then admitted to the disciminator c rcuii IP 401
incorporating the dual diode 12-19(61h2P). Detected pulses from the t1?st1,.
nator output are fed to the two-stage pulse amplifier incorporating dual
triode D2-2016N3Ph here they are amplified and fed to the control tdb??.
the right half of tube 12-21(6112P), where second detection of the AFC ou
takes place.
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Ntail
Negative voltage from L2-21 tube is fed to the repeller electrtd tt he
klystron.
If the fluctuation of IF exceeds the klystron adjustment limits:, thei
the blocking oscillator pulses from left half of L2-2It6N2P) tube art fed
right half of L2-20(6N3P) tube, thus replacing the pulses arriving from 1a
discriminator. The AFC cireuit forms control voltage which main Lain the
klystron frequency at a voltage that is 30 Mb higher than the manetron
frequency.
During reception9the pu3ses reflected from target are admitted Into,.
waveguide through the ATR tube L2-12(RR-21) through the mixing chamber of t
receiver, where crystal diode type'D4056, D4056A(D2-3, B2-ll.) act as licxerv?
TO the mixing chamber of the receiver are also admitted continucusly ci
lations from klystron local oscillator. A number of frequencies are *ormt
after mixing, from which the 50 Mc IF if separated out on the load of the
receiver mixer (input?circuit of IF preamplifier).
After passing all stages of the IF preamplifier, assembed with L3-1,
12-2(6Zh1B) tubes, the amplified signals are fed to the input of ;I:Jain-IF
plifier of the range unit.
High-voltage rectifier assembled with L2-5(6$7B) tubes su
power to modulator tube L2-7(TGI-1-35/3) at a voltage of -1450 v.
Firing rectifier is assembled with L2-10(Tkh-2) 12-15(SGM) and L' 16
(6S7B) tubes and it feeds cower to discharge tube D2,12(RR-21) at a voltaer-
of -750 v, which accelerates firing of the discharge tube during the o-,)era-
of the unit during its operation of transmission.
50X1-HUM
P 42]
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SPN
SECRET
50X1-HUM
is. Description of the operation of the unit accordinr to
the schematic diagram
TrOW frequency unifr
a) Submodulator (fig. 12)
The operation of the modulator is controlled by a sabmoclulatEr
in which voltage pulses of the required amplitude, duration, shape,
and repetition rate are formed.
The submodulator comorises a double triode type 6N1? (L2-3) ind
consists of two stages: a blocking oscillator with self-excitatirn
which occupies the left half of the tube, and a cathode repeater uhicY
occupies the right half of the tube.
The pulse from the blocking oscillator is used for manipulatd.on
of the AFC system for the emission time of the main pulse.
In order to eliminate the effect of the submodulator on the 1.-PC
circuit, a trigger pulse is sent through the cathode repeater L2-1
(6N3P).
- h3 -
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50X1-HUM
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OUA I uivi
SPN 14.4
- nmcnn
b) tilocking oscillator (fig. 13)
The blocking oscillator or pulse generator with transformer
coupling is a single-tube self-oscillating system of the relaxaticn
type with strong positive feedback, making it possible to generate
short pulsespunder certain conditions, which are close to square
pulses in shape (fig. 14).
We will begin our examination of the operation of the blockirg
oscillator from that rromenttowhen the left half of tube L2-3 (6N1?)
is blocked due to the voltage drop across resistor R2-10, which ir
caused by a discharge of capacitor C2-14; the latter was charged to
a voltage Ust with the polarity shown in figure 15.
Consequently, at this moment the voltage Ud between the rid. and
the cathode will be Ud - Ust.
Discharge of the capacitor occurs exponentially with a time
constant equal to the product of capacitor C2-14 and resistor H2-3.0.
We will disregard the voltage drop in the secondary winding of VIE
transformer since its resistance for the discharge current is very
small.
At the moment ti there is a point when the voltage in the grid
reaches the value Edo, after which the tube opens and the anode
current ia, which will pass through the primary winding of the trans-
former, begins to build UD (fig. 15).
A voltage U2 will be induced in the secondary grid winding.
The ends of the secondary winding are connected in such a manner that
SPN 45 the voltage in the grid increases as the anode current increases.
This voltage has positive polarity relative to the cathode. This
voltage increase in the control grid of the tube of the blocking
oscillator causes an even greater increase in the anode current. En
addition, there will occur a decrease in the voltage of the anode of
the tube due to the increased voltage drop in the primary winding of
the transformer.
The increase in anode current causes a further increase in
voltage in the control grid of the tube, and this, in turn, causer an
even greater increase in anode current, etc. This process of
avalanche-type build-up of anode current is called a direct blocking-
process.
50X1 -HUM
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NOW
Awe
1 (
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Nair
SPN 4 7
SECRET
50X1-HUM
Naturally the anode current cannot build up infinitely since it is
limited by the characteristic of the tube.
It should be noted that in the beginning, the rate of voltage
build-up in the grid increases.
The increase in grid voltage is linked to a corresponding decrease
in voltage in the anode of the tube, which becomes less than the
voltage in the grid of the tube. This situation gradually moves the
operating point of the tube toward that region of the tube character-
istic where, because of the decrease in steepness of the anode current
characteristic and the increase in steepness of the grid current
characteristic, the necessary self-oscillating conditions for the
existence of the blocking process no longer exist.
As a result of this there appear forces which lead to a decrease
in the rate of build-up of voltage Ud in the grid, although voltage U
itself continues to increase. With the increase in voltage in thE gr
the steepness of the characteristic assumes smaller values and, cense-
quently, the forces causing the decrease in the rate of build-up cf the
voltage increase. It is therefore natural that finally, at a particuisl.
moment t3 very close to the moment tz , the voltage at the grid reaches
a maximum Ud max, after which there follows a stage of comparatively
slow change in the voltage Ud at the grid (the flat part of the pase)
as well as all remaining voltages and currents.
At the onset of this stage the voltage at the grid begins to
decrease rather slowly; however, this decrease does not at first cause
a noticeable weakening in the anode current due to the small value of
the steepness of the tube characteristic in this region. Since ir this
stage Ud> 0, and the voltage at the anode is sufficiently small, a
rather large grid current commensurate with the anode current pastes
through the tube. As a result of this current, capacitor C2-14 charges,
leading to an increase in voltage U. With a decrease in voltage at
the grid, the operating point of the tube gradually returns to the
region of the characteristic in which the steepness assumes greater
values.
At a certain moment t% , the steepness of the characteristic
reaches a value at which the condition for existence of the blocking
effect is again satisfied. The decrease in voltage at the grid begins
to cause a more noticeable decrease in the anode current of the trbe,
dill 48 which leads to a voltage decrease in the windings of the transferrer.
As a result of the decrease in U2 there occurs a further more intensive
decrease in the voltage IJ at the grid of the tube; this causes a stit_L
greater decrease in the anode current and, in this manner, a blocking
- 47 -
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50X1-HUM
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8PN 50
SECRET
50X1-HUM
effect phenomenon similar to the one described above but acting ir the
opposite direction originates. This "reverse" blocking effect leads t)
a sharp drop in voltage at the grid of the tube and a rapid blocking ot
of the oscillator tube.
At the moment the tube is blocked, short-duration emf's of rather
high value and opposite polarity, which rapidly drop to zero, are
induced in the transformer windings. After blocking of the oscillator
there begins a stage of slow discharge of capacitor C2-14 in the grid
circuit; this is the point at which we began our examination of
processes in the blocking oscillator.
The duration of generated pulses is determined by the parameters
of the grid circuit of the tube and the parameters of the pulse trans-
former. The pulse repetition rate is determined basically by the
time constant of the discharge circuit of capacitor 02-14. Vhe pulse
repetition rate may be regulated by changing the value of resistor
R2-10. The output voltage of the blocking oscillator is taken from
an auxiliary winding of the pulse transformer, applied to the grid of
the cathode follower (the right half of tube L2-3), and represents
positive pulses with an amplitude of 220 v, a duration of 5 to 8
microseconds, and a repetition rate of 300 pps.
Resistor R2-13 is connected in parallel with the output windlng of
the pulse transformer ad forms the ballast load of the winding.
A positive pulse for triggering the AFC system is taken from this
winding of the pulse transformer. The trigger pulse is applied ts
triode L2-4 (6N3P) which is introduced into the circuit for the purpose
of decoupling the input circuits of the AFC system and the modulator;
the triode also plays the role of a limiter.
In the cathode of L2-4 (6N3P) is the divider R2-20, R2-44 frsm
which the trigger pulse passes through the coupling capacitor
to the screen grid of tube L2-18 (6Zh1P) of the second rf amplifioatitt
stage of the AFC system. Figure 14 shows the pulse at the output of
the blocking oscillator.
In order to decrease the influence of the blocking oscillator on
the other circuits of the radar, a decoupling filter consisting
resistor R2-9 and capacitor C2-13 is connected to the oscillator k,node
circuit.
- h9
JECRET
50X1-HUM
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_
S
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cnv4 ui IRA
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SECRET
SPN 53
v) The cathode follower
50X1-HUM
Positive pulses from the blocking oscillator are taken from the
auxilliary winding of the pulse transformer and applied to the grid of
the cathode follower (fig. 16) in order to avoid the effect of thE
modulator on the blocking oscillator of the submodulator and for the
purpose of matching the anode resistance of the load and the output
resistance of the blocking oscillator.
The load resistor i2-12 is selected so that the amplitude of the
derived pulse will be no less than 150 v. Figure 17 shows the pulse
at the output of the cathode follower.
g) The modulator
The modulator of the transmitter is based on a circuit with an
artificial pulse-forming line LF2r1 which discharges through the
thyratron type TO1-1-35/3. The circuit of the modulator is given in
figure 18.
Operation of the modulator may be divided into two stages: the
recharging stage of the pulse-forming line, and the resonance
recharging stage of the line.
During pulse recharging of the line a negative square pulse eith
an amplitude of 5,500 v is formed in the secondary winding of thapulee
transformer and is applied to the magnetron, which forms the load of
the modulator.
For an explanation of the principle of operation of the modulator
we will convert the modulator circuit to an equivalent circuit (fig. 19..
A negative voltage of -1,450 v is applied to the cathode of the
thyratron from the high-voltage rectifier, which comprises tubes
(L2-5, L2-6).
At the moment a positive trigger pulse from the subnodulator
arrives, the thyratron is fired by the -1,450 v source and the pulse-
forming line recharges in such a manner that, toward the end of the
recharging period, the voltage in the line is equal in magnitude to
the voltage at the cathode of the thyratron; that is, it is equal to
the voltage of the -1,450 v power supply. When the recharging period
terminates, the thyratron is extinguished and the pulse-forming line
slowly begins to recharge through the following circuit the pulse-
-52-
50X1 -HUM
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SECRET
50X1-HUM
1. forming line, the primary winding of the pulse transformer, and choke
SPN 54 Dr2-1 (fig. 20).
Iwo
SPN 56
A diagram of the discharge circuit of the line is shown in
figure 21.
The recharge circuit represents an oscillatory circuit whose
capacitance is the total capacitance of the pulse-forming line LFT-1
and whose inductance L is the inductance of the choke Dr2-1 (the
inductances of the pulse-forming line and the primary winding of the
pulse transformer may be disregarded because of their small value in
comparison with that of choke Dr2-1). Thus, the parameters of the
oscillatory circuit are selected so that the period of natural oscil-
9
lations is equal to T = , where Fs is the pulse repetition rate
of the submodulator.
Figure 22 shows a graph of the voltage change in the pulse-
forming line. It can be seen that, for a period of natural oscilla-
tions equal to T, the trigger pulse of the submodulator arrives at the
moment when the voltage in the pulse-forming line, as a result of the
resonance recharging, of the line, becomes equal to-* 1,450 v. With the
arrival of the positive pulse, the thyratron fires and the period of
pulse recharging begins.
The trigger pulse to the grid of the thyratron passes through a
coupling capacitor 02-16 and a resistor R2-15 which serves as a limiter
of the thyratron grid currents.
Resistor R2-14 is a leak resistance in the control grid circuit
of the thyratron.
Figure 21 shows an equivalent circuit of the pulse recharge eye-.
tem of the line. It may be seen from the picture that at the moment
the thyratron fires there are two series-connected emf's in the
recharge circuit -- the emf of the battery E and the emf of the pulse-
forming line, which is charged to the voltage of the power supply.
These erels are loaded vith two resistances -- the characteristic
impedance of the line and the resistance of the load, which is equal
to the characteristic impedance of the line. Thus, a voltage approx-
imately equal to twice the voltage of the power supply is applied to
the anode of the thyratron relative to the cathode. In view of the
equality of the characteristic impedances of the pulse-forming lire
and the load, this voltage will be, in the ideal case, equally dirtri-
buted between them, and in this manner a voltage will appear at the
load which will be equal to the voltage of the power supply.
- 53 -
50X1-HUM
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5UX1 -HUM
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SECRET
58
SPN 60
From the theory of infinite lines it is known that a line leRded
by a resistance forms within it a square voltage pulse, the duration
of which is determined by the recharge time of the line whic'1, iv
turn, is determined by the parameters of the artificial long line.
Thus, the best shape of the pulse and the greatest efficiency will be
obtained by completely matching the characteristic impedance of tie
line with the load resistance. (The resistance of the fired thyratrol
may be disregarded due to its small size).
The modulator of the unit uses a two-element artificial line of
the link type. Its parameters are:
a)
b)
c)
d)
total inductance
total capacitance
characteristic impedance
shaped pulse duration
(for a level of 0.5)
C
.P
16.5 microhenries
4,300 picofarads
68 ohms
pt
0.65 microsecond
As was noted above, the magnetron is the load of the modulator.
But since its resistance for the given operating conditions lifters
sharply from the characteristic impedance of the line and is equal to
1,300 ohms, direct connection of the magnetron to the modulator would
lead to mismatching of the line, a significant decrease in effici==mcy.
and to sharp distortion of the shape of the modulating pulse.
In order to avoid this, the magnetron is connected to the modula-
tor through the pulse transformer Tr2-5, which makes it possible o
match the characteristic impedance of the pulse-forming line with the
resistance of the magnetron. In this case the resistance of the
primary winding of pulse transformer Tr2-5, taking into account the
total resistances of its auxilliary windings, is equal to 68 ohms.
that is, the pulse-forming line is loaded by a resistance eoual to it14
characteristic impedance.
In addition to performing this matching function, the pulse
transformer is used to obtain a pulse in the secondary winding ham-ing
an amplitude several tires greater than the voltage pulse in the 'pri-
mary winding (on the order of 5,300 4- 5,700 v). This makes it pw,sibli
to use the sources of lesser voltage and, consequently, also simp3ififs
high-voltage protection of the circuit of the unit.
The pulse transformer has a double secondary winding through 'thick
the filament voltage passes to the magnetron. Such a filament saroly
circuit makes it possible to use the transformer as a filamcnt-sutoly
transformer under a relatively low voltage. In order to create a
closed circuit for the variable component of the magnetron anode rur-
-55-
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50X1-HUM
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5 01
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;3ECRET
Aar
SPN 61
50X1 -HUM
rent, leads 3 and 5 of the secondary winding of the pulse transformer
are blocked by capacitors C2-21, C2-221 C2-231 and C2,7.24, forming a
so-called filament supply circuit with a middle grounding point (fig.
As a result of the fact that the moment of firing of the thyratrrr
relative to the pulse of the submodulator blocking oscillator flurtuatc-
from pulse to pulse within the limits of 0.03 to 0.04 microseconde, it
is impossible to provide synchronous operation of the entire station
from the pulses of the submodulator; therefore, a pulse, in addition
to the modulating pulse of the modulator, is taken from auxilliary
winding 7-8 of the pulse transformer for the purpose of synchronizing
the operation of the station. This pulse has a duration of 0.6 Micro-
seconds and an amplitude of 80 volts. (See fig. 18). In order tic
avoid parasitic oscillations, the winding is shunted by resistor 12-2t.
To eliminate "noise induction", the trigger pulse is picked up with tte
aid of shielded conductors.
The trigger pulse is taken from winding 7-8 of transformer Tr2-5
(fig. 18) and is fed through the right half of tube L2-4 to the
ranging unit of the station for synchronization. Load resistor R-41
is specially selected to match the amplitude of the trigger pulse.
A 3 kv spark discharger L2-8 R-1 is connected in parallel with
the primary winding of the pulse transformer. In the case of varlous
malfunctions, such as in operating the modulator with no load (tht
magnetron not generating), the spark discharger does not permit tre
voltage in the pulse-forming line to exceed 3 kv.
A small inductance L2-8 (5 microhenries) is connected to the anoet
circuit of the thyratron for the purpose of improving the operatitig
conditions of the thyratron.
In parallel with the thyratron filament is capacitor C2-171 ivhiet
serves to eliminate stray pulses from the filament and the filamert
winding of the transformer.
The modulator circuit as used in the given unit has substantial
advantages over other circuits with artificial pulse-forming liner.
This may be seen in the fact that the voltage at the high-voltage ooirt:
of the modulator does not exceed the voltage of the power supply (1,45\: 7),
while the amplitude of the pulse at the load is equal to thE voltage ci
the power supply.
In other circuits the voltage in the line and at the anode al the
thyratron is twice the voltage of the power supply (with respect to
"ground"), while the pulse amplitude at the load is equal tc the value
of the power supply voltage.
-58-
50X1 -HUM
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SPN 62
SPN 64
d) High-voltage rectifier
The high-voltage rectifier operates in a voltage doubling
with two thyratrons type TKh-2 (L2-5, L2-6).
A schematic diagram of the rectifier is given in figure 24.
50X1-HUM
The rectifier and voltage doubling circuit consists of two serier-
connected single-phase rectifiers operating with a capacitive load.
One of the single-phase rectifiers is formed by the seconder,
winding of transformer Tr2-4, thyratron L2-5, and capacitor C2-18e;
the other is formed by the secondary winding of transformer ?r2-!&..
thyratron L2-6, and capacitor C2-18b.
Thus, for one half-period the voltage of the secondary winding
charges capacitor C2-18a through thyratron L2-5, and for the other --
capacitor 02-18b through thyratron L2-6.
The total voltage with respect to the frame which is taken from
point "a" is equal to - 1,450 v.
The modulator thyratron is the load of the rectifier.
Divider resistors R2-22, R2-23, and R2-24 (1 Megohm each) axe
-
connected in parallel with capacitor C2-18. The purpose of the divider
is to create a capacitor discharge circuit; that is, it is the ballast
load of the rectifier.
These resistors protect the capacitor from disruption during no-
load operation of the rectifier.
To provide step regulation of voltage at the output of the high-
voltage rectifier, the. primary winding of the transformer is made with
taps. By switching the tap, which is connected to a 115 v, 40U cpt
network, it is possible to change the voltage in the secondary wirdine,
increasing it or decreasing it relative to the position of the switch
by changing the transformation ratio.
ye) Firin. rectifier for ATR tube
The firing rectifier for the ATR tube is tube TKh2 (L2-10)
(fig. 25).
A voltage of - 750 v is applied to the anode of TIM2 from the
-59-
FTT
50X1 -HUM
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cor'a
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411111111v
SPN 66
SECRET
secondary winding of transformer Tr2-10.
50X1-HUM
The rectifier operates in a single half-period rectification
circuit.
The rectified voltage is taken from capacitor C2-31. This vtata
is applied to the firing current stabilizer of the ATR tube, whidL
comprises tubes L2-15 (SG-5B) and L2-16 (6S7B).
The stabilizer circuit maintains the load current during chares
in input voltage as well as during changes in load resistance.
Triode 6S7B is used as a control tube in the stabilizer. In ordti
to compensate for large negative bias formed by a voltage drop at the
cathode resistor R2-391 a constant reference voltage is applied tc tht
control grid circuit of the control tube (tube L2-15 (SGB) is used af
the source of the reference voltage). This voltage acts counter to tYE
voltage in resistor R2-39. The voltage is taken from potentiometer
R2-78. By using the potentiometer to regulate the bias in the cortrol
grid, it is easy to establish the required load current. Resistor
R2-39, which is connected to the cathode circuit of the control trhel
represents a current feedback element with which current stabilizEtior
is achieved during changes in load resistance. Let us assume thEt
the load resistance increases for some reason. This causes a decr,iase
in the anode current and a voltage drop in resistor R2-39, and, cEnse-
quently, a decrease in segative bias at the grid of control tube 12-16.
The resistance of tube 1,2-16 for a constant current will drop and the
load current will remain almost unchanged. With a decrease in loEd
resistance the bias at the grid of tube L2-16 increases, the resiEtance
of tube L2-16 increases, and the load current also remains oracticallN
unchanged.
-62-
50X1-HUM
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SPN 67
OM Ar..11
50X1-HUM
16. High-Frequency Device of the Receiver-Transmitter Unit
a) Function
The high-frequency device of the receiver-transmitter unit if
designed for generating powerful high-frequency pulses, for transvit-
ting the energy of these pulses to the antenna-waveguide system, ior
switching the antenna-waveguide system from transmit to receive, and
for converting the received high-frequency signals to i-f signals.
The high-frequency device includes the following elements:
high-frequency magnetron oscillator;
antenna switch;
receiver mixer;
AFC mixer; and
klystron oscillator.
0 The high-frequency device
In order to perforr the above functions the radio-frequency head
is arranged according to the block diagram shown in figure 26.
The antenna switch consists of a main waveguide with a dischzrge
tube for blocking the magnetron (BP) and one wide-band iischarge tubt
for protecting the receiver (RZP).
When transmitting, a high-power pulse from the magnetron causes
the discharge tubes to disrupt and fire and an infinitely large resis-
tance is created at the inppt to the receiver channel (according to
the rule of quarter-wave sections of long lines); in this case aLL tht
SPN 69 energy of the magnetron passes to the antenna without significant
losses, and the receiver mixer is blocked to the degree that the
leakage power to the receiver channel cannot cause damage to the
crystal detector.
During reception of the reflected signal from the target, the
magnetron channel is blocked by the transmitter blocking discharge
tube, and since the tube is located at a distance which is a mult-_ple
of half a wavelength in the waveguide from the receiver protection
discharge tube, an infinitely large resistance is formed at the input
of the magnetron channel which prevents weak-signal losses in the mag-
netron branch.
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50X1 -HUM
Thus, the received signal enters the mixer of the receiver without
significant losses. At the same time, the mixer receives high-frequenc
oscillations from the klystron oscillator which operates continuously
at a frequency differing from the received signal by the value of the
intermediate frequency.
Due to the nonlinear characteristic of the crystal detector, an
i-f signal voltage appears at its output and passes to the i-f ampli-
fier.
Simultaneously, the firing voltage is applied to the trigger
electrode.
There is a separate channel for the AFC system which is connEctec
ik 70 to the magnetron channel through a cutoff attenuator. The purpose - of
the attenuator is to weaken the power diverted to the magnetron can-
nel to the level required for normal operation of the AFG mixer.
SPN 71
Operation of the AFC mixer is identical to that of the receiver
mixer.
The difference frequency signal taken from the output of the
AFC mixer enters the input of a special circuit, and from the output
of this circuit a control voltage moves to the reflex klystron. henct,
the frequency of the klystron oscillator is regulated by the AFC cir-
cuit by changing the voltage applied to the klystron until the differeu
between the frequencies of the klystron and the magnetron equal the
intermediate frequency.
In this manner, up until the moment of arrival of the signal re-
flected from the target, the frequency of the klystron oscillator is
adjusted to the frequency of the received signal.
v) The magnetron oscillator
The range-only radar "Kvantn uses a type MI-158 multicavity
magnetron to generate high-frequency oscillations.
At the present time multicavity magnetron oscillators are the
basic type of radar oscillators for the centimeter-wave band. Th_s c
be explained by the fact that multicavity magnetrons have a numbe- of
advantages over other types of high-frequency oscillators. :or in
stance, multicavity magnetrons are capable of providing large valles
of power in a pulse of comparatively small average power, and thei
have a high efficiency which may reach 70%.
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50X1 -HUM
The magnetron oscillator operates in a pulse mode with a pulse
repetition rate of 800 Cps and generates high-frequency pulses having
a pulse power P; 5 kw. -?requency of the high-frequency oscillations
is 9,370 ? 45 Mc.
The principle of operation of the magnetron may be represented by
a diode in which the flow of electrons is acted upon not only by on
electrical field, applied between the anode and cathode, but also a
magnetic field which is created with the aid of permanent numets and
directed perpendicular to the electrical field.
As a result of the action of the electrical and magnetic fields
on the flow of electrons, the trajectories of the electrons are dis-
torted. Their movement may be represented by the curves shown in
figure 27.
This curved electron flow, in passing close to slots which con-
nect the cavity resonators with the cavity between the anode and
cathode, releases its energy and excites high-frequency oscillations
in the cavity resonators which, by means of coupling loops, are fed to
the main waveguide.
The cavity resonators and the slots form the oscillatory system
of the multicavity magnetron; the shape of one resonator with a slot
is shown in figure 28.
Thus, the cylindrical portion may be considered an inductance L,
SPN 72 and the flat portion -- the capacitance of an oscillatory circuit
whose natural frequency f. may be approximately determined from the
formula:
f - 1
In view of the presence of many resonators in the magnetron, its
oscillatory system proves to be very complex and, as is known, has not
one but several resonance frequencies. In order that oscillations of
only one frequency be excited in the system and that the frequency of
the oscillations be stable, so-called cavity resonator strips are used.
The cavity resonators are arranged in a circle in a heavy copper
block. A coupling loop is inserted into one of the resonators to con-
duct the high-frequency energy to the main waveguide, which transtits
it to the antenna. One end of this loop is soldered to the wall of
the resonator and the other end is placed within the waveguide. in
inner wire of the line passes through a glass seal which serves to
hermetically seal the inner space of the magnetron.
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I -1 11,JIVI
ri s
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SHIM
SW 75
50X1-HUM
In the middle of the anode block is a cylindrical heater cathode,
which has a comparatively large diameter, providing a sufficiently
large active surface necessary to obtain a large emission current. On
both sides of the cathode are shielding discs which improve the st-uc-
ture of the field in the interaction space.
The cathode is fastened within the magnetron by means of holders
which serve simultaneously as the cathode and filament leads.
A node on the holder performs the function of a high-frequano
choke and prevents the flow of high-frequency energy through the file!.
ment leads.
A permanent magnetic field is created with the aid of a magnetic
system consisting of a horseshoe magnet.
When a negative pulse equal to 5,500 v flows to the cathode OF
the magnetron, the magnetron is excited and generates high-frequency
oscillations which, with the aid of the coupling loops, are fed to the
wave guide.
For convenience and safety of operation, the anode of the mave-
tron is grounded (since it is not convenient to insulate the anode
because of the large dimensions involved), and a modulating T)ulse of
negative polarity is applied to the cathode.
g) Schematic diagram of radio-frequency head
A schematic diagram of the radio-frequency head is given in
figure 29.
The radio-frequency head consists of three basic parts: the
antenna switch, the oscillator (heterodyne), and the mixer device.
We will examine each of these parts.
Antenna Switch
The antenna switch, as was noted above, consists of discharge
tubes for blocking the transmitter (BB?) and for protecting the
receiver (H213).
Discharge tube type RR,-SO is used as the RBI' and wide-band
dt-
charge tube RR-21 is used as the HZ?. Both types are designed to
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SECRET
411?10.
SPN 77
SPN 78
50X1-HUM
operate in the required frequency range.
For purposes of irproving matching, a part of the main wavefuidf
in the plane of RZP is made in the form of a 120-degree degenerate
Y-joint. To accelerate the discharge, the RZP is equipped with
special firing electrode which is supplied by a current-stabilised
firing rectifier.
Uhen operating the antenna switch under low-temperature cartel-
tions, special attention should be devoted to one other parameter of
the discharge tubes -- the recovery time. It is known that recovery
time increases sharply with a decrease in ambient temperature. This
means that the sensitivity of the radar set at negative temperatures
will be considerably less than required during the recovery Perioi of
the discharge tube, which corresponds to a range of 1,000 to 2,00.7) m.
Therefore, a warming system is used in the antenna switch to achive
a normal recovery time.
The warming system comprises a heating element and a thermo-
regulator.
A schematic diagram of the system is given in figure 29.
The heating element and thermoregulator are placed in (1.schal.ge
tube RR-21. The magnetron blocking discharge tubes do not have specie')
heaters since they have less effect on the total recovery time cf the
antenna switch.
Let us examine the heating system for RZP.
Under normal temperature conditions when the set is switched on,
contacts 2 of the thermoregulator are open and the heater is switched
off.
The thermoregulator has been adjusted so that contacts 2 close
at a temperature of no less than * 5?C, and open at a temperature
greater than + 40%. The heater for the discharge tube are switched
on in this manner through contacts 2.
As soon as heating begins, the temperature in the shell if th?
discharge tube begins to rise.
Thus, the heater system will automatically maintain the tempera-
ture in the shell of the discharge tube within limits up to + 40%
with ambient temperatures up to - 60?C. A bimetallic strip relay is
used for the thermoregulator.
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50X1-HUM
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co
Declassified in Part - Sanitized Copy Approved fo
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SECRET
SPN 79
50X1-HUM
Mixer Device
The mixing device is designed as a balancing network. High-,
reliability silicon detectors type D405-B, D405-BP are used as mi.;:ers
in the receiver channel, and type D405-A, D405-AP in the AFC channel.
The use of a balancing network makes it possible to suppress
klystron noises at the output of the mixer; thus, there is a gain in
sensitivity on the order of 2 db. The balancing part of the mixer is
a slotted bridge. The bridge connections are compact and wideband.
The slotted bridge is formed by two sections of a rectangular
waveguide with a common with a common narrow wall. In this C011117104i
wall is a slot which forms a coupling section between the two wm-m-
guides (fig. 30).
The properties of the slotted bridge are completely identica2 for
any arm under conditions when the remaining three arms are loaded witl
matched loads.
If a power is applied to arm "1", it will be divided in half be-
tween arms "3" and "4" and will not go through arm "2".
This property of the bridge is explained by the fact that tar
types of waves originate at the boundary of the coupling section vhich
compensate for each other in arm "2".
An important property of the bridge is that the wave in arm h"
leads the wave in arm "3" by 90 . Thus, the power levels in both arms
are identical. With a phase shift differing from 90 , the division
of power in the arms is unequal.
In the practical design of the slotted bridge, equal power distri-
bution at the average frequency of the waveband is achieved by tuning
the slotted bridge with a capacitance control screw.
When the slotted bridge is used in the balancing mixer, crystal
mixers are attached to arms "3" and "4". A mixer circuit with revPrsei
polarity of the crystals is used in the described radio-frequency qead
(see fig. 31). This drawing shows only the high- and intermediate-
frequency circuits.
Let us examine how klystron noise suppression occurs in this 2ase.
The physical nature of i-f noises of the klystron are the same as for
the received i-f signal. At the same time, the noise components or
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SECRET,
si)ii 81
, -
SPN 82
quimr"
50X1-HUM
the noise spectrum of the klystron, the frequency of which differe
from the carrier frequency by the value of the intermediate frequency,
are mixed with the carrier in the mixer and produce klystron noise.
which have been converted to i-f, at the output of the mixer. The am-
plitude of these noises is proportional to the power of the klystron.
From here their further amplification in the i-f amplifier is undesir-
able, since they increase the total noise of the receiver and decrease
sensitivity.
Mathematical analysis shows that if the signal were directed into
the same arm as the oscillations of the local oscillator, there wruld
appear at the output of the mixer with reversed polarity crystals
i-f voltages which would be equal in amplitude but opposite in phase.
If the signal were directed into one arm and oscillations into
an adjacent arm (see fig. 31), the i-f voltages at the output would be
equal in amplitude and in phase.
Following this explanation it is clear that the oscillator noises
entering the same arm as the carrier are cancelled at the output, while
the i-f voltages of the signal are added, since the oscillations of the
signal and the oscillator enter different arms of the slotted bridre.
Figure 32 shows that in the d-c component circuit both crystals
are connected in series and the same current passes through the crys-
tals. Therefore, it is possible to control the current of any one
crystal. This control is carried out by measuring the voltage dro)
across a known measuring resistor (in our case, 100 ohms.)
Series connection of the crystals in the d-c component circuit
provides for automatic positive field current in one crystal from the
current of the other. Such a mixing circuit has a balancing action.
No matter to what extent the crybtals differ in d-c resistance, im]e-
dance at high frequencies, and in other parameters, when they are 2on-
fleeted in such a circuit the current in the crystals becomes comolatelr
identical and the parameters of the crystals approach each other.
This latter condition is very necessary from the viewpoint of
the degree of suppression of klystron noises.
As seen from the circuit (fig. 29)0 the balancing mixer has a
single-cycle output and is connected to the input of PU?Ch (i-f am)li-
fier) by a single high-frequency cable.
From the viewpoint of coupling to the input of the i-f amplifLer
and measuring crystal currents, a balancing mixer with reversed cr%s-
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OUA I -riuivi
SO
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6PN 83
50X1-HUM
tal polarity in no way differs from a single-cycle mixer.
In the AFC mixer channel (after the cutoff attenuator r71)
fig. 29) is a varbbb resistive attenuator [6] for adjusting the a_ena:
amplitude from the main waveguide to the necessary value. The cw;off
attenuator is a circular opening in the waveguide. The attenuation of
the cutoff attenuator depends on the diameter and length of the openinr.
An Alsifer probe is inserted into the opening of the attenuator to
suppress high harmonics of the magnetron signal.
The variable attenuator is a pertinax plate covered with carT)on.
Maximum attenuation of the attenuator is not less than 25 db with a
standing-wave ratio of no more than 1.4. Attenuation of the cutoff
attenuator is equal to 51 2 3 db.
Current in the AFC crystals is measured in the same manner in
the receiver crystal -- with the aid of a special filter box consistirf
of capacitors and inductances.
Oscillator
Klystron K-27 is used as the local oscillator in the r-f hear of
object RB6-2M.
R-f oscillations from the oscillator [143 enter the head threugh
a special coaxial waveguide junction [is] (fig. 33) which is connected
to one of the arms of the distributing slotted bridge. The energl of
the oscillator is distributed in the slotted bridge between the AFC
and the receiver channels. The fourth arm of the distributing slttted
bridge is loaded with a matched absorption load made in the form ef a
wedge of special shape. The standing-wave ratio of the load is no
greater than 1.2 [16).
The oscillator and antenna channels are bypassed through the use
of the balancing circuit of the mixers, which eliminates the oassawe
of energy from the oscillator to the antenna and the signal to the
oscillator.
Regulation of the power of the klystron entering the mixer is
accomplished by the use of variable attenuators r4,53 of the laminated,
knife-type. Attenuation is introduced by lowering the plates into the
waveguide. Attenuation is not less than 25 db with a standina-wav?
ratio not greater than 1.4. The absorbing plates improve the matcling
of the klystron load.
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50X1-HUM
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SE011ET 50X1-HUM
jaw
SPN 85
50X1-HUM
d) Design features of the radio-frequency head
A general view of the radio-frequency head is given in figure 34.
In order to decrease weight, the entire radio-frequency head is
made with aluminum weveguides. The slotted bridges, attenuators, and
the detector section are made of 10 X 23 mm waveguide sections.
For compactness, the entire receiver section of the radio-fre-
quency head is designed in the form of a four-component subassembly.
All four detector sections of the two balancing mixers are located in
a line, and replacement of the crystal detectors may be carried out
from one side of the radio-frequency head.
When replacing the crystals it is necessary to make sure that the
type and polarity of the crystals correspond to the type and oolarLty
specified in the r-f head. When this is not done, crystal current will.
be very small or close to zero and sensitivity will drop sharoly.
The r-f head has tvp controls for regulating the crystal current
of the receiver and AFC mixers. The controls have lock nuts.
r 7 87
The local oscillator sectiomis attached to the unit separateLy
from the remaining part of the r-f head and is connected to the latter
by means of a coaxial waveguide junction.
The radio-frequency head also has a filter box consistin of ,a-
pacitors and inductances which are connected to the crystal curren-,
measuring circuit.
17. Automatic Frequency Control of the Klystron
,WC (Figure )j2)
The frequency of the magnetron oscillator and the klystron oscil-
lator may change during operation of the radar. This change may be
caused by a change in ambient temperature, pressure, power supnly
voltages, or for other reasons.
At the same time a -change will occur in the intermediate freemen-
cy, which is equal to:
C int. f kly. - rnag.
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50X1-HUM
SPN 88
SPN 90
where: f int. is the intermediate frequency, kly. is the frequency
of the klystron oscilletor, and C mag. is the frequency of the Tiamv-
tron oscillator.
The AFC system is intended to maintain a constant intermediote
frequency by electronically adjusting the frequency of the klystron
oscillator to that of the magnetron oscillator. The AFC system ()Pent
from the natural pulse of the transmitter. For this purpose there it
a branch in the main waveguide line through which part of the enyrgy
of the magnetron oscillator is diverted to the mixing chamber of the
AFC. This branch of the waveguide line is a cutoff attenuator wnth ay
attenuation on the order of 50 db.
This attenuation. is determined by computing the maximum leakage
power to the crystal which will provide for its normal operation.
The load of the crystal detector is the input circuit of the AFC
circuit in which the difference frequency voltage is derived.
Operation of the A?C is of a "searching" nature.
The "searching" AFC is capable of tuning the klystron oscillator
within wide limits.
The AFC circuit functions in the following manner:
At the moment of emission of a main pulse, a difference freqaency
pulse passes from the crystal mixer to the input circuit, which is
tuned to a difference frequency of 30 Mc.
The first stage of L2-17, comprising tube 6Zh1B, is the i-f amol:_-
fier whose anode load is the standard band circuit TR2-8, which is
tuned to a frequency of 30Mc.
The bias in the control grid is automatic and is formed by a drop
in voltage across resistor R2-47. Capacitor C2-39 is blocking for thu
difference frequency. Capacitor C2-38 blocks the screen grid and is t
filter for. the * 150 v circuit.
The amplified difference frequency pulse passes to the contrel
grid of tube L2-18, which is the second i-f amplifier stage. Amp3ifi-
cation of this stage is controlled by changing the negative bias Et
the control grid of the tube. A change in bias is made with the tid
of potentiometer R6-5 ("AFC Gain") located on the control panel
In its normal state tube L2-18 is closed and opens only at the
iGECRET
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50X1-HUM
SPN 90 moment of emission of the main pulse, when a positive AFC trigger
pulse (80 v) is applied to the screen grid.
Thus, the AFC system operates only on the basis of a natural
signal, and will not respond to other signals.
From the anode load of tube L2-18 -- a resonance circuit coil:or-1.-
sing coil L2-20, the output capacitance of the tube, and the moun-Ang
capacitance, a signal passes to the discriminator, which is based on
tube L2-19 (6Kh2P) (Fig. 35).
The discriminator is one of the basic elements of tae AFC system:
it converts the change in difference frequency to changes ir ampl:_tude
of a video pulse, the value and sign of which vary accorlin4- to chang?
es of difference frequency relative to a frequency corresponding to ti(
zero error signal of the discriminator or, as we will henceforth call
it, the crossover frequency.
The input circuit of the discriminator (coil L2-21 and caoamtor
C2-46 and C2-47) determines its most important characteristics: /he
width of the frequency band (the frequency separation of the Positive
and negative humps of the frequency characteristic), and the crosc-
over frequency.
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P
50X1-HUM
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OVRIDVVII
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?irate
Resistor R2-59 and capacitor C2-49 make up the load of one d'ofie , 92
of the 12-19 tube, while the resistor R2-60 and C2-50 make ito th-
of the second diode of 12-19.
These loads are connected symmetrically with respect to the (is-
criminator, while the voltages on them are subtracted. Conseouently
the output voltage of the discriminator represents the Iifferencn of
voltage taken off the load of each diode of the 12-19.
Shown in figure 36 are all stages of the transition from the
schematic diagram of the input circuit to the equivalenc; cIrcult.
According to the diagram, capacitor Ca is equivalent; to the
capacitance introduced in the circuit by both diodes. Capacitorf
C2-46, C2-47, and C3 make up a triangle which is replaced by ar
equivalent star of capacitors Cl, Ci, Csh.
Resistors R2-57, R2-58 make 'up the "middle point" of tte eoi3
12-21, and are replaced by one resistor Ra, directly conneeted wtJh
the middle point of the coil 12-21.
Shown in figure 37 is the complete equivalent circuit of L e
discriminator. In tht circuit, preceding the discriminator.
t;he
L2-18 tube amplifier is replaced by an equivalent generator "T."
Half of coil 12-21 And capacitors Cl and CII make uf two
resonant series circuits, tuned to frequencies fl = 28 and f, =
megacycles.
With a change in tho value of the inductance of the colt L2-21,
a certain retuning of ercuits I and II is possible, and
consequently, a change 7in certain range of frequencies for ;ie
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nr,reorm
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crossover of the discriminator response. Since the 1-factor of
the circuits is differene, amplitude asymmetry of the negati
and positive humps of the frequency characteristics results.
Since in the circuit: under examination only the positive hultiD
of the frequency charaet4eristic of the discriminator is rsed,
the amplitude asymmetry :ef the humps is quite permissible and
is even desirable.
As a result of apelying a frequency difference pulse on its
input, a video pulse [4signal-error"] is generated at the auteet
of the discriminator. The magnitvde and sign of the error signal
depend entirely on the extent of deviation at a given instant, of
the difference of heterodyne and magnetron frequencies from the
intermediate frequency. The characteristic of the discrferdneter
is shown in figure 38.
If the difference ft-fluency is less than the crossover freluerey,
the error signal is positive and is all the higher in amplitude tie
greater the difference frequency differs from the crossover- frequincy,
and vice versa, if the difference frequency is greater than the
crossover frequency, then the error signal is negative and is all the
higher in amplitude the greater the difference frequency ditTers :rom-
the crossover frequency. From the output of the discriminator thc
error signal passes through capacitor C2-51 to the control grid oe
the video amplifier tube 12-20-a L6N3P] and from the plate load of
this amplifier R2-62 to the second stage of the video amplifier
[1,2-20-b].
50X1 -HUM
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From the plate of L2-20b the video signal passes through
capacitor C2-56 to the control grid of the regulator tube L2-21b
[6N2P], which operates as a grid-leak detector.
We examine the operation of the grid-leak detector shown in
figure 39.
If on the last video amplifier a positive video pulse appears,
then capacitor C2-56 starts to charge up with respect to the C2-56
circuit: the grid-cathode section of the tube L2-21b, C2-57a,
ground, the 150-volt power supply, R2-66, R2-65, C2-56.
The time constant of this circuit is small, since during he
time of duration of the video pulse the capacitor is able to
charge up almost to the amplitude value of this signal.
After termination of the video pulse, the capacitor starts to
discharge through the circuit: internal resistance of the tube
L2-20b, ground, capacitor C2-57a, resistor R2-75, capacitor C2-56.
The time constant of this circuit is large, and capacitor
C-56 is not able to discharge completely before the arrival of the
next pulse.
The discharge current causes the appearance on resistor R2-75
of a voltage, applied negatively with respect to the control grid,
which drops the current through tube L2-21b.
Because of this, the voltage drop across resistor R2-73 is
lowered, and the negative voltage at the output and feeding the
klystron heterodyne repeller rises, which increases the generating
frequency of the klystron.
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C\trl
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Therefore, the nex pulse arriving in the APCh (AFC) s/stem
will have a higher di.fference frequency. In the discrimina or,
this pulse is converted to a video pulse with a smaller amwitude th-/,
the preceding video pulse. This is clear from the freouene?r charactc,
of the discriminator (figure 38).
Since capacitor C2-56 is not able to discharge completely be ore
the arrival of the next video signal, it is only given an additirnal
charge from this signal, but of a smaller magnitude.
In the event of arrival of the pulse at the input, the l'fference
frequency which equals "() megacydles, in the grid detector is est,blil-e4
balance, i.e., the capacitor is given an additional charge e?,ual o
1:,he discharge prior to the arrival of the next video pulse. 4t t ,e
output of the AFC, in this case, the voltage, which is fed '0 the
klystron repeller, is changed little and the klystron frequency
remains, in fact, fixed.
If the difference frequency is changed in a manner such that
becomes larger than the crossover frequency, then the circuit of
the AFC converts to the search mode. On the output of the dtscriiy
and subsequently, on the output of the video amplifier, will appear
negative pulses, which will not provide an additional charge to ca
C2-56.
Consequently, the negative voltage on the grid of tube 12-21b will
be lowered, which will lead to an increase in the plate current of
tube L2-21b.
Moreover, the negative voltage on the cathode of the ,ube
1,2-21b will be reduced so rapidly and reach such a value that the
blocking generator tube (1,2-21a1 opens.
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Awe
The blocking generator [12-21a] operates in a wait mode.
The oscillations of this generator, from the cathode of the tupe
12-21a through capacitance C2-54 and resistor R2-59, are applied t)
the grid of the video amplifier [tube 12-20b].
Since there is a zero potential on the control grid of this tuJe,
the positive pulses of the blocking generator are clipped because 3f
the grid currents of the tube, while the negative pulses, which werepreviously differentiated, are amplified.
From resistor R2-65, which is the plate load of tube 12-2r)b,
the amplified pulses of positive polarity are fed to the grid
detector [tube 12-21b).
As a result of the detection of these positive pulses,
capacitor C2-56 charges.
Moreover, the negative grid bias of L2-21b increases, which
leads to a drop in the current of this tube and an increase in the
negative voltage at the cathode.
This increase in negative voltage reaches a value such that the
blocking generator tube Is cut off.
After this, capacitor C2-57 begins to discharge slowly until the
blocking generator does not open again.
This "search mod&r will be continued until the difference
frequency remains equal to 30 megacycles. Now, the APCh (AFC) cir'hait
is automatically returned to a regulating mode, while the blocking
generator at this moment is cut-off.
A potentiometer R2-71 serves to establish the necessary value
of the reference voltage for the A7Ch search, with the aid of which
ix"
the voltage on the cathode of the blocking generator is regulated.
This voltage is established in a manner such that its value ondi
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to the middle of the generating region of the klystron.
A general view of the APCt((AFG) is shown in figures 40 and 41
The schematic diagram is sIpml in figure, 42.
18. Structural Design of the Unit (Figure 43)
The receiving-transmitting unit is structurally on a welded chassis,
which is rigidly fasteded hy screws from the front panel. The chassis of
the unit is housed in a cylindrical case on which a ring moves to fasten
the. case to the front panel of the unit. The maximum diameter of the
unit D 240 millimeters, the length L 368 millimeters.
To provide the unit with the necessary air tightness from the
internal side of the front panel, there is a circular groove containilg
a rubber lining.
The flange of the case is fastened to this lining by the movable
ring using screws with washers and springs. There are fins on the Case
to increase the cooling surface.
On the front panel of the unit are located:
a) 17-pin sealed plug-type connector for connetion with the
intermediate cable.
b) Sealed waveguide outlet for connecting the antenna-waveguide
system to the receiving-transmitting unit.
v) Sealed high-frequency plug-type connector which serves to (SPI 101)
connect the PUPGh with the main UPCh.
g)
outlet.
d) Nipple for pumping air.
Sealed high-frequency plug-type connetor for blanking pulse
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Viler
Perpendicular to the front panel is fastened the chassis Edell
has openings of complex configuration through which pass the )rojeatin;
sections of the radio frequency head, the magnetron, and the -711V1 ,pe
of the thyratron.
Located on the chassis from the top are: intermediate frequeLcy
preamplifier in the font of a separate subpanel, APCh (AFC) subp
recharge choke, pulse transformer, K-27 klystron, switch for iriantfy
winding of high-voltage transformer, shaping line.
Located underneath the chassis are: radio frequency head,
magnetron, high voltage transformer, filament transformers, a
n
The magnetron generator is located so that the magnets with t e
oscillatory system of the magnetron are located in the lower part
of the unit and the lead of the magnetron filament and the !at.io,e
are located in the upper part of the unit.
V. Range-only Radar Receiver Unit
19. Function of Unit
The range-only radar receiver unit is designed for:
a) Amplifying intermediate frequency signals and eonver;,in
them to video signals
b) Search, lock-cm, and range tracking of the target ii th-
operating range, and generating a voltage proportional to ihe
range to the target I'm two operating modes.
v) Signalling tJ.1t. lock-on of the target
In the absence of 3ignals reflected from the target, ttl't uni is
in the search mode. The search range is set by the "RB-SV switch
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located in the pilot's cabin. With the appearance of a signal reflected
from the target, the unit is switched to the tracking mode and generates
a voltage which is proportional to the distance to the target. With the
simultaneous appearance of several targets in the zone, swept by the
range-only radar, the system for determining dltstance will lotk-on,t1
closest one of them, and a voltage will be established onihe output
of the unit proportional to the distance to it.
20. wig ,TECHNICAL CHARACTKRISTICS OF THE UNIT
a) Search limits
in "A" mode -- 200-3,200 meters
in "B" mode -- 800-7,500 meters
b) 'Dependence of range voltage on distance to target:
in "A" mode Ud [v3 195 - Dim)
20
in "B" mode lid [v] ... 195 - Dim
0
c) Maximum statistical error of introducing range voltage:
in "A" mode -- no more than = 15 meters in a distance
range of 400-2,000 meters
in "B" mode -- no more than i 100 meters in a distance
range of 800-7,000 meters
v) Search frequency -- 1 cycle ? 0.2 cycle
d) Resolution -- 200 meters
e) Storage time -- 2-3 seconds
ail) Triggering lag time of relay RZ-3 -- 1-1.5 seconds
z) Dimensions of unit -- 300 x 152 x 180
i) Weight of unit -- 4.7 kilograms
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21. Description of Unit Operation Based On Functional Diagram (figure
a) Search Mode
The negative triggering pulse, taken off of the winding of the oulsc
transformer of the modulator [unit RB6-2M3, arrives in unit Rai-3, and
through diode L3 is fed to the plate of the multivibrator for triggering
a "fast saw" [L3-13]. The multivibrator is triggered by this pulse
and generates a positive square wave of at least 50 microseconds,
triggering the "fast saw" generator. The "fast saw" generator
[L3-14] generates a negative saw-toothed pulse which is sent to the
comparator circuit. The frequency of the saw-toothed pulses of the
"fast saw" has the repetition frequency of 800 cycles, the amplitude
changes from 195 to 35 volts.
In addition to saw-toothed pulses at the input of the comparison cir. tp 109]
cult, a voltage arrives which is generated by the search circuit. Th s v( -
age also changes according to the saw-toothed law, but approximately 'i0,0(C
times slower than the voltage of the "fast saw" [frequency of 1 cyclei.
This voltage is sometimes called "slow saw", and the circuit generatirg
this voltage, the "slaw saw" generator. The "slow saw" voltage varies it
the range from 135 to 20 volts.
As a result of comparing the "fast saw" and "slow saw" voltages,
negative pulse is generated on the plate of the comparator diode ri3-]A,
the onset of which, as the "slow saw" voltage decays, lags more and mo-e
behind the triggering pulse of the transmitter. This pulse is amplified
by L3-22a, differentiated, and again amplified by L3-16a. The pulse an
the plate of L3-16a triggers the range pulse blocking generator 1,3-16h.
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11 ILIIVI
The blocking generator"' generates a pulse with 0.7-microsecend
duration and an amplitude of 100 volts called the range pulse.
This pulse is fed to the time discriminator circuit on tee sersen
grid of the coincidence tube [L3-18] and through a 0.4 mierosecond'
delay line to the screen grid of L3-18. The pulse taken fror Lne ceia3
line is sometimes called the "second" range pulse.
As is clear from figure 7, in the search mode, as the "slow s
voltage diminishes, the range pulses are shifted in the direc-tion
of an increase in the range. Therefore, with the operation e_ the
"slow saw" generator, they pass periodically, once a second, iiroh
the entire distance range.
From the plate of the receiving channel [L3-7]-, the noise voltage
arrives at the output of the circuit for automatic gain control 01 cols
mar The circuit maintains a constant receiver noise level with a rie.-
tion in external factors [power supply voltages, tube aging, etc.
To eliminate the influence on the operation of the AGC noise circuit
reflected signals, the circuit is modulated by a negative pue abui
50 microsecond duration, applied on the suppressor grid of L
-9.
The windings of reLays R3-1, R3-2, and R3-3 in the seareA mod-,
are de-energized, the relays are in the released state.
b) Tracking Mode
The pulses reflected from the target, preamplified n tht
receiving-transmitting unit, arrive at the input of the intermediate
frequency amplifier [L-1--L3-51. Amplified in the UPCA (IF amp.) arc
detected by the second detector [L3-6a], the target signal arrives a4
the input of the video amplifier [L3-7a]. After amplificaton throw;,,
the cathode follower L3-(b, the target pulse is fed to the input of
-16
the time discriminater [ 131 ET
L3-18, 100 -
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No coincidence circuit and the recharging diodes with tie
capacitance integrator (sometimes called the diffference detectorj
make up the time discriminator. In the search process, ;he range
pulses, passing through the entire range band, at a certain time -
coincide with the target pulse. Negative pulses appear on tie
plates of the coincidence tubes, feeding into recharging diodes sold
the automatic lock-on circuit. Relay R3-1, which is the prmary
actuator of the automatic lock-on circuit, operates and engages
relays R3-2 and R3-3.
After operation of all relays, the unit converts from the sca2cn
mode to the tracking mode. One of the relay contacts feeds a sigdal
of -27 volts to the sigbt and the "lock-on" signal lamp in he
sight goes on.
Starting from this instant of time, the position of the range
pulses is not controlled by the "slow saw" voltage, but by the
voltage produced by the control unit circuit and depending o tht
magnitude and sign of the error arriving at the input of the duplex
integrator from tie., time discriminator circuit.
Relays R3-2 and R343 switch over the elements of the "slow sew"
generator circuit [L3-R3], and the latter becomes the second
integrator of the control unit.
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IMF
The voltage on the plate of the first integrator [L3-261,
which until lock-on is determined by the "wait" voltage taken _yrf
of the grid of L3-26 from the divider R3-36 and R3-133, after
relay operates will be determined by the magnitude and sign of
the error current from the output of the time discriminator.
Upon lock-on on the target, the target pulse usually
coincides with the second range pulse at first. Now, the time
discriminator circuit produces the negative error current [in the
direction from the first integrator and to the time discriminator
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4.1 01
0:A ar
i
oa cr? tr?
0 GI 0
a
Ce%
E ea t41
4.) CJ csJ
0 in in
C.) 0 p44
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Tube L3-26 in this case cuts off and the voltage on its plate
increases, which results in the opening of relay L3-23 and, sub-
sequentlyjthe reduction in plate voltage. This voltage
controls the range pulses through the cathode follower L3-22b.
The reduction in this voltage brings about the shift of
range pulses toward a large range, that is, the range pulses co-
incide with the target. During the movement of the target, for
example, on the approach p;reater- agreement takes place between
the target and the first range pulse. Moreover, the sign or the
error current becomes positive, tube L3-26 opens, and tube L3-23
cuts off. The voltage on the plate of L3-23 rises, which causes
the range pulses to move toward the same side and at the same ra:e
as the target pulse.
Range tracking is effected in this manner. The properties
of the control unit circuit with two integrators make is possible
to track a target moving at constant velocity without dynamIc
error, while the voltage on the plate of the first integrator
(L3-26) is proportional to the velocity of the target.
The voltage controlling the movement of the range pulses and
taken, off of the cathode follower L3-22b, during tracking is
proportional to the distance to the target. This voltage goes
through the cathode follower L3-21a and is fed: a) in mode "A,"
to the sight computer, b) in mode "B" to comparato.r. unit K-F.
Relay R3-3 trips within 1-1.5 seconds and the lag of the
servo mechanism of the range unit increases, as a result of which
fluctuations in the reflected pulse do not affect the range voltage.
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At the same time, relay R3-3 transmits a smoothing signal to unit RBb-5
which increases the lag of the servomechanism of the velocity unit.
To maintain a constant target signal level, there is a device for
automatic pulse gain control in the range unit. The pulse arrives
at the circuit input from the amplifier plate of the automatic lock-on
[L3-19a].
This pulse is amplified, detected, and as a negative bias is fed
to the control grid of the UTCh tube through the cathod follower L3-10.
It is essential that the reflected signal be maintained at a
constant level to provide accuracy in determining the distance to the
target.
The operation of the ABU noise circuit is identical in the searca
node and in the tracking mode.
A detailed description of the operation of the elements in the
ABU circuit is given in the section titled "Receiver".
22. Description of the Operation of Unit Based On Schematic Diagram
(Figure 73)
a) Trigger Multivibrator [Figure 491
For normal operation of the "Fast Saw" generator it is necessary thai.
the pulse have an amplitude of at least 25 volts and a duration of 50 Juicy(
seconds. This pulse is generated by the multivibrator, which is asseMb1e6
on the basis of a circuit with cathode coupling to tube L3-13 [6113D].
In the initial state the right half of the tube is open, since
there is a zero potential on the control grid and the
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cathode, through R3-69, is connected with a-150-volt source. Thr!
current of the right half of the tube, flowing across the cathorte
resistance [R3-69], creates a voltage drop across the cathode
closing the left half of the tube. The initial voltage from the
divider R3-126 and R3-127 is applied on the grid of the left hall'
of the tube. The magnitude of this voltage is chosen so that
taking account of the :bias in the cathode the left half of the
tube will be reliably closed in the initial state, and the multi-
vibrator will be triggered dependably upon application of the
triggering pulse. The mnitivibrator is triggered through the
cut-off diode L3-12b, which is necessary for clipping off the p
tive portion of the triggering pulse.
With the presence of a positive blip in the triggering pulse,
the multivibrator becomes critical with respect to the magnitude
of the triggering pulse and,consequently, undependable in opera-
tion.
The triggering pulse is fed through the diode to the plate IS f 1 1 71
of the left half of the tube and through the capacitor C3-47
to the control grid of the right half, thereby closing it.
The current in the right half is diminished, lowering the
voltage drop across the cathode resistance of the multivibr, or,
and the voltage on the plate lode R3-68 is increased.
The lowering of the cathode bias opens the left half
the tithe and results in a voltage drop on its plate. The voltage
is transmitted through C-47 to the grid of the right half,
facilitating its blanking still more. As a result of the process
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described, the multivfbrator is opened "reversed", the left half
of the tube is opened, and the right half is closed.
Capacitor C3-47, which in the initial state was charged to
nearly the full voltage of the power supply, begins to discharge
through the left half of the tube which is open. The capacitor
discharges through the following circuits: internal resistance
of the left half of L3-13, R3-69, internal resistance of power
supply, R3-70. In flowing through R3-70, the discharge current
creates a voltage drop across R3-70, which maintains the right
half of the tube in the blanked state.
As the capacitor discharges, the discharge current graduall,T
decreases, leading to a reduction in the voltage blanking the
right half of the tube. At a certain instant of time this vol-
tage becomes, in terms of absolute value, less than the tube
blanking voltage, and current appears in the right half of the
tube. The appearance of current leads to the reduction in volteJA
on the plate of the right half of the tube, and consequently
to the blanking of the left half. In turn, the blanking of the
1?,,,eft half of the tube facilitates more effective opening of the
right half, as a result of which the multivibrator reverses
to the initial state in which it was round before the arrival
of the triggering pulse. The time constant of the discharge
circuit C3-47 .was chosen so that the blanking time of the right
half of the tube is 60 microseconds.
As a result of this, a positive square pulse is separated
on the plate load of the right half of the tube with the indicat_d
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length and an amplitude of 20-30 volts.
This pulse is fed to the circuit of the "Quick Saw's generat(r.
To monitor the normal operation of the multtyibrator, the cathode
of L3-13 leads out tc a control point designated as 1 1 and
located on thP -P-1-nn-F panel of the unit.
b) Fast Sawtootb.acneT4IorAFigkirs,p]
Used as the " fast Saw" generator in the unit is a linearly-
dropping voltage generator with plate-grid capacitance. The " ft
saw" generator is made 11:0 of a tube L3-14 [6Zh2P] and has two
operating modes.
In the first mode, mode "IC, the generator produces a negatite
pulse with a linear leading edge of 25-microsecond length; and
mode "B", of 60-microsecond length [figure 511.
The change in pulse length is effected by connecting additional ICTN 1191
resistors to the circuit of the control grid of tube L3-14, which
are located in unit 1(.-6, R6-l7, R6-18, R6-19.
In mode A, they are shorted-out by relay R6-3 [contact b 1-91.
In the initial state, the tube is blanked through the plate
circuit because of the application on the suppressor grid of a
blanking voltage of -25 to -30 volts. The screen grid circuit of
the tube is open so that the total plate supply voltage [+200 volts]
is applied to the control grid through R3-72 and R3-73. The
potential of the control grid is equal to approximately il volt.
Capacitor C3-49 is -charged to nearly the total voltage
fixed by the slider of the "zero range" potentiometer so that
the voltage drop across the grid-cathode section can be disregardel
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With the transmission to the protective grid of a positive
pulse from the triggering multivibrator, the tithe is opened
through the plate circuit and capacitor C3-49 starts to discharu
in the following manner.
a) In mode "A:', internal resistance of L3-14, internal
resistance of power supply,R3-78, R3-79, and R6-11.
b) In mode "B", internal resistance of L3-14, internal
resistance of power aupply, R3-72, R3-73, R6-11, R6-17, R6-18,
and R6-19. In the first instant the voltage on the plate of 1SPN L',";1
L3-14 starts to drop sharply. This reduction.in voltage is tran3-
nutted through C3-49 to the control grid of the tube, increasing
its internal resistance and lowering, consequently, the discharge
current of the capacitor. Since in the initial stage the voltage
on the control grid is equal to approximately to +1 volts and the
tube is campletely closed at -6 volts, the initial negative vol-
tage jump on the plate and on the grid of L3-14 is approximately
4-5 volts.
After the initial jump the linear discharge of capacitor
C3-49 begins. The discharge current flows through the discharge
resistors indicated above and creates a voltage drop across them,
controlling the internal resistance of the tube. It is permissable
in the process of discharge that the discharge current start to
diminish. It is evident, moreover, that the voltage drop across
the discharge resistors diminishes and the tube L3-14 opens*
The opening of the tube lowers the resistance in the discharge
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lowe'
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circuit and consequently increases the discharge current, returning it
to the initial value. An increase in discharge currents cause blank-
ing of the tube which also results in the establishment of the
initial current value. Because of the presence of such control over
the internal resistance of the tube, the discharge process, While the
discharge of the capacitor at constant rate results, as is known, in
a linear reduction in voltage on its plates.
Actually, the voltage on the capacitor plates during discharge an
be expressed by the relationship: JcUCt) ()01-dr
Sine to obtain a proportional relationship between the range
voltage and the distance to the target it is essential to have a
linear reduction in voltage, it is evident that the second term of
the right side of the equality must be a linear function of time,
that is: (1
jto I.,(t) obit
Solving this equation, we obtain: constant, that it is the
necessary linear drop in voltage will be obtained during the discharve
of the capacitor at constant current. During the discharge of C3-49
the voltage on the plate of the tube is reduced approximately te
20-25 volts, so that with an additional reduction in plate voltage
the tube ceases to control the discharge current. The length of the
saw-toothed pulse on the plate of L3-14 for the values of the circuit
element used by us is 25 microseconds in mode "A" and 60 microsecondE
in mode "B".
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Upon termination of the positive pulse on the protective grid,
the tube again closes through the plate circuit. Capacitor C3-49
discharges through R3-74 and the grid-cathode section of L3-14, and the
entire circuit returns to the initial state. The initial voltage on .he
plate of L3-14 is regulated with the "zero-range" potentiometer R6-15
located in the unit K-6. The steepness of the saw-toothed pulse is
regular by changing the timp constant of the discharge circuit C3-49.
Added to resistors R3-72 and R3-73 are the following:
a) In mode "A", a variable resistor R6-11 ["scale of range An]
b) In mode "B", resistors R6-18 and R6-19, and potentiometer
R6-17 [scale of range "B"], Which are housed for convenience of
regulation in unit K-6 also.
Since the voltage on the plate can be expressed by the relationsnip:
II L.z) where Ea is the voltage on the plate of L3-14 before
arrival of the triggering pulse; Eg is the voltage supplied across the
resistor in the control grid circuit [ 200 volts], t is time, R is the
discharge resistance, C is C3-49, it is clear that regulation of the
"zero range", effected by a change in Ea does not have any effect on
the steepness of the pulses, which is regulated by the change in the
value of the discharge resistor Prange scale], and in turn does not
affect the "zero range".
Thus is provided independent regulation of "zero" and "scale"
which is extremely convenient for operation [figure 51].
Resistor 1(3-76 in the screen grid circuit is designed to
limit the current on the second screen grid during periods of
- 115 -
ip 3.24]
Ip 125]
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inactivity, that is when the tube is blanked through the plate
circuit.
As evident from formula (2), the elements which determine
the steepness of the "saw" in mode "AP are C3-491 R3-72,
R3-73,and R6-11, and in mode "B", R3-721 R3-731 R6-17, R6-18,
R6-19, and R6-11. To maintain a constant steepness with changes
inthe surrounding temperature these elements are thermally com-
pensated: R3-73 and R3-72 are made from manganin which has a
low positive temperature coefficient, while for C3-49 type
K2K-3"1/V with a small negative temperature coefficient was selear:ed.
As a result, the quantity RC, which has an affect on the steep-
ness, remains constant with a change in temperature, which is
essential for providing a minimal number of errors in mode "A".
Diode L3-25b is designed to reduce the length of the flybac]:
I, it
of the saw and to reduce the influence of leakage which is
harmful under conditions of interaction of humidity on the
accuracy of computing the range. Because of the diode, the
steepness of the flyback "saw" voltage, as can be seen in
figure 52, increases clue to
the increase in voltage Ea, whicE
leads to a reduction in flyback time.
The effect of leakage can be represented by an equivalent iSPN 61
resistor Ry connected between the plate of L3-14 and the frame.
In the absence of a diode, the leakage results in a change in
voltage on the plate by a quantity: Olity where Ra is the plate
load of L3-14, Ry is ?the equivalent leakage resistance.
This may cause an inadmissable error with respect to range.
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The presence of a diode results in a reduction of this error to a
value which can be disregarded even for substantial leakage.
v) The Slow Sawtooth Generator [Figure 53]
The "view saw" generator [search circuit] is designed to
generate in the target search mode a slowly decaying saw-toothed voltage
with a frequency of about 1 cps. The function of the "slow saw"
generator is performed by the tube L3-23 [6N2P] and L3-22b [6N3P],
which in the search mode act as a transitron generator of relaxation
oscillations [in the tracking mode these tubes function as the second
Integrator].
For convenience of examination, we assume initially that the
blanked state of the tube L3-23 in the plate circuit. Moreover,
there is a voltage on the plate which is determined by the divider
R3-124, R3-125. Since the control grid is connected to ground
through R3-104, the tube opens and the plate voltage begins to
decrease. This reduction in voltage is transmitted to the control
grid through the cathode follower L3-22b and capacitors c3-59,
C3-71 and, by increasing the negative bias, it prevents a rapid drop
in voltage on the plate. The process occurring in the circuit is
quite similar to the operation of the "fast saw" circuit, only
in this case the discharge of the capacitors 1C3-59, C3-711 occurs
through the equivalent resistance of the output of the cathode
follower circuit.
Thus, in the process of discharge of c3-59, C3-71 a small
negative voltage is maintained on the control grid. When the plate
voltage reaches a value of 20-25 volts, as in the "fast
P 1283
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Name
sawIt circuit, the tube L3-23 ceases to control the dischare'e ai
the drop in voltage on the plate is retarded. Consequently, th
negative bias on the control grid of L3-23 is reduced. The re-
duction in voltage on the control grid causes an increase in tho,
current on the screen grid. The screen grid current, flowing
through resistor R3-107, increases the voltage drop across this
resistor and the screen grid potential drops.
The reduction la ilotential is transmitted through C3-73 to
the suppressor -grid of L3-23 and reduces the plate current if
tube. The reduction in plate current causes a rise in potential
on the plate, and because of the couNing through L3-22b
C3-59, C3-71, an increase in potential on the control grid.
This causes an additional increase in screen grid current and
the complete blanking of the tube through the suppressor grri.
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The plate voltage rises rapidly and the process begins again. Connec-
tion of capacitors C3-59 and C3-71 directly between the plate and
grid of L3-23 and through the cathode follower made it possible to
lower the charging time significantly. If in the "quick saw" circuit
this time is considerably greater than the discharge time, then
in the given case the situation is reversed. The capacitors are
charged through the small internal resistance of L3-22b and the plate
voltage of L3-29 increases, in practice, gradually.
This is essential to provide quick fly-back of range pulses after
which, in the search process, they achieve a maximum range. The
quick fly-back guarantees locking on the target only with the
movement of the range pulses in the direction of lengthening, that
is locking on a close target. The presence of the divider in the
plate circuit of L3-23 is specified by the necessity for limiting the
start of the search for the preliminary locking on a main leakage pulse.
The filter C3-74, R3-106 facilitates stabler operation of the "slow
saw" generator.
The relaxation frequency is determined by the values of C3-59, C3-71,
and R3-104 and is equal to one cycle. This corresponds to a search rate
of approximately 10,000 kilometers per hour.
g) Comparator Circuit tFigure 54]
The comparator circuit dtermines the instant of equality of the val-
ues of the "fast saw" and "slow saw" voltages, and as a result, provides
for the delay-triggering of the range pulse generator. The delay time is
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OUA I -riuivi
determined with respect to the main pulse. The circuit consists of 131
a comparator diode, a compensation diode, and a two-storage )1Lse
generator. Used as the comparator diode is the left half of
[Fig. 55].
The "fast saw" voltage is applied to the cathode while the "slo,,
saw" voltage [in the search model] or the range voltage [in te
tracking mode] is applied to the plate through the R3-77-.
Since the voltage oft .?he cathode is greater than on the ;late,
the tube closes and there is no signal at the output. However, as
soon as the "fast saw" voLtage becomes less than the "slow sa " vol age
taken from the output of the duplex integrator, the diode opens anog a
negative pulse appears on its plate.
The start of this pulse, which is determined by the e ualluy of
the "saws", shifts ir the directior of a larger delay with respect to
the main pulse as the "fa-;1, saw" voltage reduces. From the plqte c'
the comparator diode, the pulse is fed through C3-51 to the re1-41. of
L3-22a, the pulse ampl1fi2r. 1?. positive pulse with an amplitut of
more than 100 volts is generated or the plate of L3-22a [IM].
Because of amplificelpn. the steepness of the leading ed?;e Mi
.-Lase is considerably greater Than on the grid, and the past is
almost square. From the pLate of 1,3-22a, the pulse goes Lo tne
control grid of the second pulse arplifier L3-16a [6N311, thrcul.h
the differentiating circut'. C3-53 End R3-79, which is ess-ntial for
rttducing the length. The second stage increases the steepness of tAe
leading edge of of the puLse even rore. This pulse, taken from the
-122-
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-tmr,
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50X1-HUM
Nor
plate of 13-16a, goes to the control grid of L3-16b throuvi
pulse transformer Tr3-7 and triggers the range pulse block
Because of the large steepness Of the leading edge of the
pulse, the the instant of trIggering of the blocking generator does ly
depend heavily on the fluctuation of the feeding voltages, ehanes
in tube characteristics. etc. nis facilitates a reduc ir e*r.or*
in determining the range.
Since the instant of opening of the comparator dtode der
the range-pulse delay, or precise operation of the entire inf1
is essential that it, PW far as possible, also will not depe 0 (In
the supply voltages, tube characteristics, etc. The volt-amere
characteristic of the diode is shown in Fig 55. It is know that
under the influence of ehanges in the filament voltage ad -le di /-
aging, this characteristt "drifts", that is, it is shifted ffor
example, to the position shown in the figure by the dotted linel.
Moreover, as can be seen from the construction, an error octurs ir
the instant of comparison A t . This error enters directly into
the over-all error of measuring the range.
To reduce the i fluere-
of external factors on the instant of comparison a compersating
diode is employed. For small negative voltages between the ,)late
and the cathode a current appears between them. Therefore, e.'crn
with the comparator diode closed, there will be a voltage dru aerss
resistor R3-77 determined by the current of the compensating
This voltage is directed toward the
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Now'
"slow saw" and the instant of opening of the comparator diode
occurs somewhat later [tr'l rather than t1]. Now for the shlft
in the volt-ampere characteristic, the instant of comparison shift,
to a point t'2, and the difference in time between t1 and t'2, desig
t1) is considerably less than ZS t'0.
Thus, the use f the
compensating diode stabilizes the instant of comparison. In 7-te )f
the large gain of the comparator circuit, even small influence of he
triggering pulse can result in the triggering of the blocking gene ata
at the point of zero range. In order
pulse is applied through C3-77 to the
at the initial instant of time. This
to avoid this, a small negattve
grid of L3-16a blanking the :ube
pulse is obtaiaed via the
differentiating circuit c3-77, R3-79 of the triggering pulse.
d) Range pulse generator [Fig 56]
The range pulse generator is an ordinary blocking generator
composed of the right half of L3-16 [6N3P].
In the initial state, the tube is blanked by a voltage of -l# rolt)=.
taken from the common divider of the unit and fed through R3-51 to
the control grid. At the instant of arrival of the triggering puL;
the tube opens and a current appears in the plate circuit. Th
appearance of the current results ix a lowering of voltage on the
plate of the tube. The windings of the pulse transformer are-
connected so that a reduction in potential on the plate results
in an increase in potential on the control grid. The existence
of such a circuit with positive feedback means that the plate
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current increases still more, the grid voltage rises additionally.
etc., to an instant when the tube current reaches saturation. TiR
process of "reversing" the tube occurs very rapidly and is '1,11-ed
the "blocking" process. The time for complete opening of ttle tuba
is usually about 0.1 microsecond. As a result of the termination of
the direct blocking process the plate voltage drops to almos- zer)du
to the voltage drop across the primary winding of the pulse trans'ori
while the grid voltage rises strongly and becomes positive becans,- of
the induced emf.
From the instant of time when the voltage on the grid becomes
positive, a screen grid current starts to flow and capacitor C3-5?
begins to charge.
At the end of the direct blocking process, the operating point
on the tube characteristics shifts to the region of shallow steepr ss,
that is, the change in voltage on the screen grid has almost no effect
on the value of the plat- current. As C3-55 charges the voltage on
the control grid of the Lube begins to diminish. However, slnr., tle
operating point is located on the right portion of the characterisic,
the plate current remains nearly unchanged for a certain time. Th -
flat portion of the pulse is formed during this time. With 1me,
the voltage on the control grid shifts the operating point o" the
characteristic to the region of great steepness.
The plate current is diminished more effectively, which result- in
a rise in the plate potential and, consequently, a reduction of vo.tar
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on the control grid. The latter reduces the plate current still mcre
and the inverse blocking process takes place.
The-tube is blanked and the voltage'acrbsS-capacitor c3-55 attains a
large negative value. After completion of the blocking process, this
capacitor discharges through R3-81 and the circuit returns to the initiC.
state.
The positive range pulse with an amplitude on the order of 10(
volts and a duration of 0.7 microsecond is taken from the windinv of
the pulse transformer, fed to the screen grid of the tube 1L -18 and
through a 0.4 microsecond delay line to the screen grid of L3-17.
Capacitor C3-52 and resistor R3-78, connected to the plate circuit
of the blocking generator, make up the decoupling filter which redLces tt
influence of the generator On the remaining elements of the circuit of
the unit through the power supply circuit.
AO Time discriminator (Fig 51)
The time discriminator circuit consists of a coincidence circLit,
with 6Zh5P tubes [L3-170 L3-18], and a difference detector circuit
[recharging diode] with integrating capacitanC4 consisting of 6f_fA
tubes [?13-27, L3-28].
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IMP
NEW
The function of the time discriminator is to fix the instant 'If
coincidence of the target pulse with the range pulses aid to gen ratf
a signal indicating the presence of a shift with respect to -ime
between the pulses mentioned. The circuit generates this siqnsl as 4
direct cetrrent, which is called the error current, of vary1g rattitIA
and sign depending upos the magnitude and direction of ;he migmatob
between the range and target pulses.
In the absence of target pulses, the coincidence tubes qrd
L3-18 are blanked thr3w-11 the plate circuit by the presincern t!-
control grids grids of a voltage of about -3 volts and on the sore 1 7 ;as
of a voltage of -23 volts.
Besides, the range pulses arive on the screen grids of he tue.
The pulse goes directly to tte screen grid of L3-18, and tlwoug:h )
0.4 microsecond delay lime to the screen grid of L3-17. TheEe pu ses
shift periodically with time seeking out the target. If a ptise
reflected from the target occurs on the control grids, taen tae lset
on the screen grids which are moving with respect to the range, crinci,i?
with them at a certain instant with respect to time. The.- tubes ?tem
and negative pulses appear on the plats. These pulses vo to the
difference detector oircuit {1.3-27, L3-281, and depending; tht
relationship of their amnlitudes, they are converted to An e-rrIr
current for the given direction. Taken from the resistor R3-'5 nsl
connected between the plates of 13-17 and 13-180 ia a negative pulse
which is fed through capacitor C3-57 to the control grid of the auto-
matic lock-on amplifier.
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Resistors 0-82 and capacitor C3-56 form a decoupling network ? 112
which protects the plates of the coincidence tubes from the influence
of power netwol4k. The coincidence tubes serve as the input of the
automatic lock-on amplifier.
Let us assume that after lock-on the mutual position of the
target pulse and the range pulses is as shown on fig. 58.
In this manner both coincidence tubes open, but because there
is greater coincidence of the target with the second range pulse, the
pulse in the plate of L3-17 has a
the pulse in the anode of L3-18.
Furthermore, let us agree to regard the
integrating circuit as a certain equivalent
considering the operation of this
greater amplitude and duration than
input of the double
capacitance Ci. In
element of the range unit, let us
satisfy ourselves as to the accuracy of such an assumption,
Capacitors C3-58 and C3-62, which are charged until coinci-
dence to a value approximately that of the voltage of the power
source, begin to discharge. Capacitor C3-58 discharges through the
circuit: the internal resistance of 13-17$ Cif the internal resis-
tance of L3-28. Up to coincidence, diode L3-28
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Now
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was closed by a voltage of +Tv applied to the tube cathode.
At coincidence, the diode opens, since a negative pulse with
an amplitude up to 50v is applied to the sathode and thus the
C3-58 discharge circuit is created.
The discharge current of C3-58 flows through a capacitance
C i$ and it is seen by the direction of the current that the
voltage at C i must be decreased thereby, capacitance C i discharges
(the direction of the current is shown by the unbroken arrow).
Capacitor C3-62 discharges along the circuit: internal
resistance of L3-18, resistance of negative voltage divider,
internal resistance of L3-27. Diode L3-27 also was closed
bra voltage of -11:v and is opened by the coincidence pulse.
The discharge current of C3-62 does not flow through Si
and evidently does not affect the potential at this point.
During the time between pulses, capacitors C3-56 and C3-62
are charged. The charge of capacitor C3-58 passes through
R3-82, R3-83, R3-118, R3-129. The charging current of C3-62
passes through the integrator capacitance in the direction
shown on the figure ty the dotted line.
It is evident that the potential at C will increase under
the action of this current.
In the case we have considered, the discharge of capacitor
C3-58 has a greater effect than the charge of 03-62, since there
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is greater coincidence with the second range pulse. Thus,
voltage at the capacitor will be decreased from pulse to pulse,
the total current will be directed from Ci to a difference
detector.
This current is also called the error current. This
direction of current is called negative. The appearance of
the current acts through the control unit (double integrator)
on the range pulses, and they are displaced in the direction of
greater range. Thus, a mutual position of the range pulses
and the target pulse as shown in Fig. 58 and Fig. 59 is possible.
In the given case, greater coincidence occurs in L3-18,
and the effect of capacitor C3-62 is increased. Discharging
intensely at the moment of coincidence, capacitor C3-62 is
charged by a current the value of which now exceeds the discharge
current of C3-58, and the direction of the recharge current of
of the integrator capacitance is changed.
Now the current is directed from the difference detector
to the integrator capacitance, and the potential of the integrator
capacitance increases. Let 113 call such a direction of the
error current positive.
If the axes of symmetry of the range pulses coincide with
the midline of the target (Fig. 60), the effect of C3-58 and.
C3-62 is equalized, and the potential atC i remains unchanged.
, It is evident that in this case the error current will be zero.
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Nor
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Thus, the sign of the error current is changed depending on the
direction of displacement of the range pulses relative to the
target pulse. The dependence of the value of the error currant
on displacement is represented in Fig. 61.
The error current lies on the ordinate, and the displacement
of the range pulses relative to the target in time, on the abcises.
The left branch of the characteristic corresponds to a lead of
range pulses over the target pulse. The right branch corresponds
to the delay of the range pulses.
Zk) Control Unit
(Double Integrator)
The purpose of the control unit (Fig. 62) is transformation
of the error current, which flows from the output of the time
discriminator, to a voltage which controls the range pulse delay.
The circuit consists of two integrators--tubes L3-26 (6Z1111),
L3-23 (6Zh2P), and L3-22b (6N3P).
In mode "A," the range voltage is applied through cathode
follower L3-21a (6N3P) to a sight, and in mode "III" to K-8.
The circuit diagram of the anode-grid integrator is shown in
Fig. 63.
Analysis of such a circuit shows that the dependence of
the voltage at the anode on the current in the grid circuit
can be approximated in the form:
tic( 0
'gar
/Is
ott13/
0
-- MURES - 1111-
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If we consider the circuit of the fast sawtooth generator which is
a special type of integrator (Fig. 61), it is evident that the voltttge
Ua is supplied to the input of differentiating circuit RC, at the ot_tpui
of which there is a voltage which drops at resistance RI i.e., U?d.
For such a circuit the following relationship holds true:
In our case:
Pvykh
Uyykh(out) a at
Ul(range) Ed =
d__Ua = Ud -Ed
-
RC
RC
Integrating both parts of this equation, we obtain:
t
= Co - dt
C j
i.e., the equation of the integrator.
In the case Ed Coast, and disregarding UdI we have:
U C
a - - 0 -
St idt Edt
RC
where t ? 0; Ua = Co, consequently,
Ua =uao Et
RC
equation for the fast sawtooth generator.
The integrator equation rakPs it possible to determine all the
prpperties of the circuit.
i. e.? we obtain the
For further description, let us recall that:
1. 0;dt = Coast; 2. asdt = at; 3. Stat.dt =
52 I
c it 1
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CRT
It is seen from elese general mathematical expre si
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when the current in the erid circuit equals 0, the vol ,ae
the tube anode does not ehanee since both sides of 4146 ecue- -
are constants. Tn the oeesence cf P constant current e
grid circuit, the voltaee at the anode drops linearly wieere
positive, or increases :nearly were i is negative.
It is easy- to deriee a physical explanation of the or0,-,:ec
in the integrator circuet, considering the charge and diech?
of the equivalent integkator capaeitance Si (Fig. 65).
A positive current (in our case "error current") chere(e
the integrator capacitaree, the voltage across it increpeles
and the tube opens.
The appearance of Ai anode current leads to a decre se
anode voltage. A. negative current discharges Ci, the pot-ere
at the control grid decreases, the tube is blocked, and -he
anode voltage increases.
The validity of repacing the resistance of the ini
input by the equivalent cFeeacitance ei is evident from th,
If We consider the circuit in Fig. 65, we see thattic:
Jea r\r A I
, 0
where : k is the amplification faetor of the tube.
Consequently, the circuit depicted is equivalent to
integrator circuit wherein-
t
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Mellowing the above-stated considerations, which pfr-
integrators in general, _et us examine the operation of t ,
actual circuit of the d)eble integrator used in the uni-.
The circuit consts-,t of two anode...grid integretors
by stabilizing circuit
Let 118 assume that Ai locking on the target, the miAeae
position of the range pLses and the target pulse is that
depicted in Fig. 9i, 1. v., the range pulses lead the trree
pulse.
As was explained d- ing examination of the operation n'
the time discriminator, negative error current flows to
integrator input in thi_ case. The presence of a negatve
leads to blocking of tube L3-26 of the first integrator, arL,
potential in its anode - ncreases. The voltage at divider
R3-1143 R3-115 increase: correspondingly.
The voltage from the common point of these resistarces
through R3-116 and 115-1.). is up-piled to control grid
which is the sec,rd integrtor. In this case the cit'
will be positive.
The appearance of i positive current in the grid ,irce
of the second integrato leads to opening of L3-23 and to
decrease in the voltage at its anode. The error current
flows to the input or -1?. first integrator during a briar
can be considered constent.
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'song*
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Then the voltage at the anode of the first integrator
will increase linearly (since Ja.d.t ). The current
c
in the grid circuit of the second integrator, proportional to
the voltage at the L3-26 anode, also will increase linearly.
The voltage at the L3-23 anode will decrease at an ever increasing
rate, since
Cat dt 4-27:
This voltage through cathode follower 1,3-22b flows to the
comparitor circuit (L3-15) and makes the range pulses shift
toward the receding side, also at an ever increasing rate.
The range pulses, shifting in this direction, go through the
matching positions and begin to lag the target pulse in time.
As we see in Fig. 61, the error current changes its sign and
becomes positive.
This leads to opening of the first integrator and a voltage
decrease at divider E3-1111, R3-115; and inasmuch as R3-115 is
connected to the point of the divider with a potential of -30 v,
the voltage at R3-116 acquires a negative value.
The current in the second integrator circuit changes its
signs and the voltage at its anode begins to increase.
The increase of this voltage leads to shifting of the
range pulses in the direction of decreased range, i. e.,
again toward matching with the target pulse.
After several such oscillations, the system reaches a
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state of equilibrium in which the range pulses match the target
pulse. In the event that the target- moves at a constprt
rate, the voltage at the anode of the second integrator changes
linearly. This will transpire, evidently, when there is a
constant current in the grid circuit of this integrator (faldt, at),
and signifies a constant voltage in the anode of the first integrator
(Fig. 63).
Changes in the rate of movement of the target pulse must
correspond to changes of current in the grid circuit of L3-23,
and consequently, the voltage in the anode of the first
integrator. Thus, the voltage in the anode of the first
integrator is proportional to the approach speed. This conclusion
can be drawn mathematically.
It is seen from the circuit that the voltage at the aikode
of L3-26 will be:
Ua,.
where: is the voltage at the anode of L3-26 when i C.
ao
i,: the current in the circuit connecting the output
of integrator I and the input of integrator II.
R3-114+R3-115
R = (R3.-116 + R3-104) R3-115
Since expression (3) is correct for integrator II, and
the voltage in its anode is porportional to the range to the
target, then, having differentiated, we obtain:
oLUdL
TIT
cLU
-a:76-
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where: C';.: c3.*69 4 c3-7;
consequently:
dad
where: is the rate of change in the range voltage,
proportional to the approach speed.
ALL
Rc
With the parameters used in the circuit, the voltage at
the anode of L3-26 upon locking--on a stationary target is
approximately 80v. Finiteness of the amplification factor
of L3-23 leads to the fact that this voltage -depends in addition
on the range from the target, although to a negligible extent.
In tracking an apporaching target, this voltage has smaller
values. At an approach speed of 300 m/See, it reackeet60 v.
But if the voltage at the anode of integrator I is constant
at a constant approach speed, this means that the error current
in this case is zero, since
cL (ODIISO
The foregoing case demonstrates that a control unit with
two integrators provides for tracking a uniformly moving target
without dynamic error, since the error current is zero only
when there is precise coincidence of the range pulses and the
target pulse. BeeidesIthis, as a result of the zero error current,
the circuit is capable of tracking *ding signals.
When the target fades out, the coincidence tubes close and
no current flaw :from the antput of the time discriminator
to the input of the control unit. Thus the same voltage remains
ro???????
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at the anode of the first integrator as during tracking of the
target. Singe this voltage corresponds to the speed of the target
until it fades out, tracking will continue at the same speed ii
the absence of a target. Upon the appearance of the target, it is
again: visible in the zone of range pulses and normal operation is
continued. Owing to the presence of leak resistance between the
grid and the cathode of L3-26, upon disappearance of the
error current the voltage at the anode usually alters slowly in
one direction or another, which leads to errors in tracking a
fading target. To diminish these changes, the capacitance of
the first intepator is switched, and within 1 4 5 seconds
after locking, becomes equal to 40,000 pf. At the moment of
locking, it is necessary to have a small time constant of the
first integrator. Therefore, up to and at the moment of locking,
the anode grid capacitor with a capacitance of 0.01 JA-f is
turned on.
A time lag 1 sec) is necessary for readying capacitors
C3-75, C3-86. During this time, they succeed in discharging
to the voltage which corresponds to the speed of the locked target.
The high value of the capacitance of the first integrator
facilitates a decrease in the effect of target fluctuations
on range voltage as a result of smoothing introduced by it.
To decrease the effect of leakage on the operation of the
circuit, tubes L3-26, L3-27, and L3-28 are placed in a hermetically
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sealed area, and are a separate, complete unit ("integrator 1").
For more favorable conditions of locking, the voltage
at the anode of the first integratbr in the scanning mode is
correspondingly set to the most probable target speed (nexpected
voltage"). This setting is made by applying a corresponding
voltage to the anode of the first integrator from divider R3-36
and R3-133.
To improve the pperation of the double integrator in the
mode of a fading target, it is necessary to select at the screen
grid of the tube of the first integrator such a voltage that
when no target is present the voltage at the anode of the first
integrator will be practically unchanged. The setting of the
required voltage at the screen grid is done with the aid of
potentiometer R3-113.
Capacitor C3-76 is intended to speed up precise matching of
the range pulses with the target. Together with R3-1I6 and R3-104,
this capacitor forms a so-called "stabilizing network", which
prevents the occurrence of a self-oscillating system, i. e.,
"oscillation" of range pulses around the target.
.The range voltage is applied from the output of L3-22b to
the grid of cathode follower L3-21a.
Upon locking, a voltage proportional to the range to the
target is applied from L3-21a to the external circuits.
z) Automatic Locking Device (Fig. 67)
L651
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The circuit of the automatic locking device is intended for
switching the unit from the scanning mode to the locking mode.
The circuit consists of amplifier L3-19b, peak detector L3-19a,
and electronic relay L3-20b.
Electromagnetic relay R3-1, type EDIUG, in the anode of L3-2C,
turns on relay R3-2, in the anode of L3-8a, and relay R3-3, in
the anode of L3-8b. The operating time of relay R3-2 and relay
R3-3 depends on the bias at the grids of L3-8a and L3-8b, which
is controlled by "delay" potentiometer R3-60.
The circuit of the contact groups of the automatic locking
relay is shown in Fig. 68.
In the scanning mode, the entire relay is in a released state.
Tube L3-20 is blocked by a negative voltage, applied to the
control grid by the "Sensitivity" potentiometer from unit 6
through resistance R3-92 ,R3-94.
Upon the appearance of a target pulse and coincident range
pulses, a negative pulse with an amplitude of around 25v
passes to the grid of L3-19. A positive expanded pulse, the
amplitude of which reaches 80i.100v , appears at the anode of
the tube. This pulse is applied to the grid of L3-19a and
charges capacitance C3-64. This capacitor discharges through
R3-92, as well as through R3-94 and R3-95, which are in
parallel with it. All these resistances have a large valu4 as
a result of which the time constant of the discharge is
incommensurably greater than the time constant of the charge.
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This leads to the fact that in the interval between pulses,
C3-64 does not succeed in discharging, and the voltage in it
increases.
The increase in voltage at the cathode of L3-19a decreases
the bias at the control grid of L3-20b, the tube opens, and the
relay triggers. ,Triggering of R3-1 causes triggering of the
rest of the relays in the unit: R3-2 and R3-3. In the event
that the target pulse fates out, relay R3-1 releases, and
capacitors C3-67 (2)e) and C3-83 (1 ,..4f), located in the
grid circuit of L3-8a, begin to charge slowly, from a -150v
source, through resistances R3-140 and R3-60.
Therefore, when the target pulse fades out, the voltage
at the grid of L3-8a decays slowly, and the relay releases ohly
after approximately 1-;-.1.5 see.
Herein is achieved the possibility of tracking a fading
target "by memory" (memory based on speed). Upon triggering of
relay R3-3 1+1.5 sec after locking, capacitors 0-75 and
C3-86 with a total capacitance of oajaf, the other end of which
is connected to the anode of integrator I, are connected to the
grid of the first integrator throu#h C3-85.
As a result of this, after connecting the "protection" .-clay
the anode-grid capacitance of integrator I increases to 0.04/af.
This makes the ranging system more persistent, i. e., insensitive to
abrupt changes of speed. resides this, the presence of a large
integrator capacitance imparts to range-only radar the property
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more precise tracking of a fading signal "by memory," which
reduces considerably the effect of target fluctuation on the
speed voltage.
A smoothing sigral (-27 v) is applied to unit R16-5
simultaneously with triggering of relay R3-3. Thus, relay
R5-2 operates, and the persistence of the speed-analysis circuit
increases, which reduces the effect of target fluctuation on
the speed voltage.
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k) Constrlictive luign of the Unit
(Figs. 6q, 70, 71)
The block is constructed on an open rectangular chassi3. There i
a depression for the IF amplifier line in the right section of the e,ase-=.
Parts having the greatest heat resistance, like the tube and tho [ an ,forf f
arranged at the tor and the resistors and capacitors are in the lower
section along the perforated panels.
The space between the perforated panels is occupied by the pv/se
former, precision resistors, and the relay. The last are easily rentived cugh
the access to the tube panels. Arranged under the IF amplifler are t(4
large components: oil?impregnated paper c'tpacitors, the delay line, End
control potentiometers. These parts are in the form of demountable ut?ts
and are easily removed from the block during repairs. The housing has a
4mW large number of openings to facilitate the cooling.
The functional circuit of the first integrator is in the form of a
separate air?tight highly moiSture?resistant removable unit.
Dimensions of the unit: 300 x 152 x 160 mm.
Weight of the unit: 4.7 kg
VI. RECEIVER
23. Purpose and Make?up
The receiver of the range?only radar "Kvant" is used to ampliVy
the deitection pulses reflected from targets and to convert them 4rnth
video pulses.
The receiver is made up of the following components:
1. Resonant ATR tuba.
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2. Receiver mixer.
3. Klystron local oscillator.
4. IF preamplifier.
5. Main IF amplifier.
6. Second detector.
7. Video amplifier.
8. Cathode follower.
9. Pulse and noise automatic gain control systems.
24. Description of the operation of the receiver with the aid at
a functional flow chart
The functional chart of the receiver is given in Fig. 73.
The pulses that are reflected from the target enter from the ante n3
into the"reception-transmission" chamber of the antenna switch, where a
resonant discharge tube L2-12 (RR-21) is used in the capacity of a discharg
tube.
From the "reception-transmission" chamber the energy of the rflee-
signal enters the frequency-mixer chamber, where a crystal rectifier of the
type D-403-V (D2-2) is used as a mixer.
In the receiver mixer chamber the frequency of the reflected sign
is mixed with oscillations of the heterodyne (klystron of the K-27 (142-9) t7pe).
After the mixing, a number of frequencies are formed, from which
an intermediate frequency is separated on the load of the receiver mixer.
The load of the receiver mixer is the input circuit of the IF pre-
amplifier (PUPCh).
Having passed the stages of the IF preamplfier, which uses tules of
the 6Zh1B (L2-1, L2-2)type, the signal reflected from the tigir enters tte
main IF amplifier, which uses L3-1, L3-21 L3-5 (6Zh1P), L34015-4 (62,h2V tbes.
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Amplified by the IF amplifier and detected by the second detector Li-6 imhelo),
the target signal, passing through the video amplifier LV-7 (6N3P) end the oath-
ode follower, is fed to the time discriminateir and the noise automatic
gain control circuit.
The pulse automPtic gain control and noise automatic rain crntrel
have a common outlet to stapes of the main IF amplfier through the
cathode follower L3-10a (6N3P).
During the transmission operation part of the energy of the main rplee
enters through the attenuator into the IF amplifier mixer, where the
oscillations of the klystron heterodyne also enter. The differenne frequ--
Pulse, according to which the AFC generates the control volter,e foci
to the klystron heterodyne, is separated on the input circuit of the autti-
matic frequency control.
The control voltage is maintained such that the frequency of the
klystron heterodyne would be higher by an IF than the frequency of the
magnetron.
25. 4ppose of the intermediate frequency amplifier
The purpose of the IF amTaifier is to amplify the IF signals whiee
were obtained as a result of the conversion of the picked-up reflected stqr04
in the crystal mixer to a level which will ensure the operation of tI4e II
detector along the linear portion of its response. The purpose of the II
detector is to convert the IF pulses inte video pulses which are furter
amplified by the video ampl1fier.
The IF amplifier is assembled with coupled circuits end conflicts of
an IF preamplifier and a main IF amplifier.
Basic tactical-teqhpical datel of the IF amplifier in a complete
with the II detector and the video amplifier
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a. The transmission band of the IF is not less than 4.5 mc.
b. The IF amplifier's amplification factor, defined as the rain
the signal voltage at the II detector input to the signal at the IF smplirer
input and for a noise level at the II detector of 0.7, is not lees than 100,t1 .
v. Sensitivity is not less than 1511v.
g. TheAamplification irregularity of the transmission band is not
greater than 15%.
d. The transmission factor of the video amplifier is 15.
26. Description of the operation of thy IF preamplifier by a
schematic diagram
latga_ineiatefr
(Fig. 73)
preamplifier represents a two-stage amplifier emoloyinp-tu
The IF
of the 6Zh1B (L2-1 and L2-2) type. At the point of entry to the IF pteamp7:t.
fier a two-circuit filter is connected by. an L-type connection.
The L-type diagram of the IF preamplifier input circuit is chosen
to obtain the smallest noise factor and the greatest amplification Under -3.
wide transmlssion band.
At the same time the L-type arrangement of the input circuit A1511i a
stable operation of the first tube of the IF amplifier during the chalge
in klystron power.
The input circuit consists of the Tr.2...1 autotransformer and tne 1a2-1
inductance. In addition, the Tr2-1 also represents inductance because its
windings have the same number of turns for a coupling coefficient e041 to
one. tonstructional realisation of this inductance in the form of a transrm
is brought about by the necessity of separating the current circuits 3f the
LP 176]
?ftv crystal mixer and the leakage current of the first IF preamplifier tithe.
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1SECRET 50X1-HUM
from
antenna
eceiver-
ransmitter
Chambe
1,2-12a2-13
and L2-14
AFC
Mixer
D2-1; D2-2
Receiver
Mixer
D2-3;02-4
AFC
2L17 to
2L21
r-
Klystron
Heterodyne:
AFC trigger
L2
--
High Frequency Assemtly
IF Pre-
amplifier
L2-1;L2-2
IF
Amplifier
L3-1 to
L3-5
2nd retecto
L3-6
AGC System
Pulse AGC
3-11 L3-10
from
automatic lock en
Fig. 73.
Noise AGC
L3-].Ob;
L3-9
from
modulator
Video Atpli-1
fier
Cathode el-:
lower
L3-7
to
time dicriteralar
rircuA
Functional Flew Chart of the Receiver
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lomo?slmi
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The adopted L-type arrangement of the input circuit is equitrale-1
to a coupled circuit which has on the mixer side inductance Ll and la,
citance C1 , and on the side of the input of the first tube, inductence
and capacitance C2.
The primary capacitance C1 is the sum of the constructive capa&itances --
the mixer chamber and the coaxial cable which connects the mixer wil7h thp 1-k
preamplifier input. The capacitance C2 is the sum of the input capaeitsre,,
of the first IF preamplifier tube and the capacitance of the mountirf, of 1.op
secondary circuit. Because the increase in capacitance C2 causes a sharr
increase in the noise factor, constructive measures are taken to reduce t-
mounting capacitances of the secondary circuit by selecting the most
compact mounting.
The anode circuit of the first tube (L2-1) is loaded on the loun J 177al
circuit Tr2-2 with various Q-factors of the primary and secondary cl-cuit.
The shunting resistors R2-2 and R2-3 are selected to obtain elue
factors for a stable amplification of the stage and a favorable pattern
frequency response.
The second amplifier stage consists of an L2-2 tube loaded on a sinele,
oscillatory circuit which. consists of series-connected inductances ATM
L2-7 shunted by an R2-6 resistor. The capacitance of the circuit is the
input capacitance of the tube and the capacitahce of the unit combined.
The output circuit is connected with the input of the main IF
amplifier through the capacitance C2-12 and a coaxial cable with a chnract
istic impedence of 75 ohms and a corresponding load at the inrut of the nwt,
IF amplifier.
An optimum correlation is selected between L2-6 and L2-7 to ontaiza
better transmission factor nnd a better pattern of the frequency response
of the transition from the IF preamplifier to the IF Amplifier.
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OUA I -riunn
Due to the fact that the cathode current passes through resistaw-a
R2-1 and R2-5, self-bias is supnlied to the grids of the amplifier tubes
The capacitances C2-2 and C2-6 shunt the IF bias resistors and in
this way exclude the negative feedback of the signal, increasing the
amplification of the stages.
Power is supplied to the screen grids and plates through a series ii1811
decoupling filter, consisting of inductance L2-4, resistance R2-7, and cADg-
citances C2-4, (22-9, and G2-11.
In addition, the resistance R2-7 lowers the initial source vDlt
150 v to a value ensuring the operation tolerance of the tubes.
The filament of the tubes is also decoupled by a filter consisting
of Inductances L2-3 and L2-5 and capacitances C2-3, C2-71 and 02-10.
The IF preamplifier is tuned in an arbitrary sequence by turning
cores, the coupled circuits T2-1 and T2-2, and the inductance L2-6.
The core screws are Ted out on the tube side of the IF nreasn11f7'pr
aubpanel.
The amplification of the IF nreamplifier on an IF frequency fs n(A. 7ess
than 17 for a transmission band of not less than 6 mc.
The IF preamplifier frequency response is represented In Fig 74.,
27. Main intermediate frequency amplifier (UPCh)
(Fig. 75)
From the IF preamplifier output, the signal enters the IF Rmridflt
-
input, employing the miniature tlibas 62111P and 62;112P (L31
To match the IF amplifier input with the characteristic ispel-
ance of the coaxial cable and ? the IF preamplifier output, a matching
load of 75 ohms, which consists of two parallely connected resistors of 15'
ohms each (R1-1 and R3-2), is connected to the IF amplifier input. F 1821
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OUA
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The capatitance C3-68 divides the automatic gain control circrit.
The coupled citcuits Tr3-1 to Tr3-5 are connected to the plate
circuits of L3-1 to L3-5 tubes with equal (4-factors.
The amplifying steps on the coupled circuits with equal Q-1"acter3
possess a more stable frequency response during a change of tubes and alter-
ations of voltage aupplies than signle circuit networks and other networke,
A necessary transmission band of each amplifying step (9 to lf) mc
is ensured by a selected relation between the windings of the plate ard gr
circuits and the shunting resistors.
All circuits are adjusted by changing the inductance by means of
movable cores in arbitrary sequence. Along the central grid circuits -)f
L3-1 and L3-2 tubes a self-regulating amplification of the IF amplif1-4. 14
carried out.
Regulating voltage is supplied from the automatic gain cflntrot gr l,
which is located in the range finder device, through the decoupling filte-
consisting of filter cella 33-1, Z3-21 R3-33 and capacitances C3-1,
and G3-31.
Along the circuits of the pentode grids of the L9-3 and L3-4: tub
the IF amplifier is blocked during transmission.
The blocking pulses are supplied from the modulator gr ie sitvatet
in the RB6-21,1 transmitter-receiver unit.
Amplified to the necesserv level, the IF signal is Tupplied tM
the diode detector which employs the left half of the L3-6 (6Zh2?) tube.
The frequency response of the basic IF amplifier, which is taken 7ouL
the output of the detector for a signal of 100 Lv at the IF input, is
represented in Fig. 76.
The frequency resmnse of the complete IF amplifier together with
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,J%-//? I -I IVIVI
the IF preamplifier is represented in Fig. 77.
The amplification of the main IF amplifier at IF is at least 10,1'
the band width at least 6 mc at an irregularity of not more than 174.
The Dower supply of he screen grids and tube plates of the main
IF amplifier is taken from the source +150 v, and to ensure the Dotimal
operation of the tubes,part of the voltage is consumed across the
resistance R3-30.
A multisectional filter, consisting of inductances L3-7 to L3-10
capacitances C3-5, C3-10, 03-14, C3-18, C3-23, and 03-30, is used for
decoupling the high frequency of the IF amplifier's screen grids.
The power supply of the tube plates is brought through the
oscillatory circuit.
The tube filament circuits are also decoupled from each other by a
filter consisting of inductances L3-1 to L3-6 and capacitances 03-3, ';3-8
0-12, 03-16, 03-20, 03-25, and C3-29.
The initial bias of the order of 2v is automatically suoulied to -11;
grids of the amplifier tubes due to the drop of voltage across the cal;ho&,
resistances R3-3, R3-61 R3-10, R3-15, and R3-19 as a result of current flow
from the tubes. To eliminate the high frequency negative feedback, i.c., .
increase the amplification, these resistances are blocked by ca iCitances-
03-2, 03-4, 03-7, 03-9, C3-11, C3-15, 03-19, and 03-21.
28. Detector
(Fig. 78)
The intermediate frequency signals are detected by a diode detector
occupying the left side of the L3-6 (6Kh2P) tube.
The main advantage of a diode detector is the linearity of it.: detto-
tion response, beginning with relatively small signal amplitudes, and the
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L310
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absence of overload of the detector by strong signals.
From the Tr3-5 circuit the signal voltage of the intermediate re-
quency is supplied to the diode cathode.
A rectified voltage of the video signal is obtained on the tesistalLce
of the R3-25 detector load, and is then supplied to the video amplifi.er g!-f.1
through the transient ciranit C3-27 and R3-26.
This transient circuit, together with the right half of the L3-6
tube, limits incoming signals with respect to their duration, a process ,on
is ensured by appropriate selection of the time constant.
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50X1-HUM
,411W
ii11111111?,"
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SPN 189
SECRET
29. Video Amplifier
(Fig. 79)
Video pulses from the detector output are further amplified
by a video amplifier which comprises the left half of tube
L3-7 (6N3P).
Active resistance R3-23, having a value of 9.1 k St, is
selected on the basis of conditions necessary to obtain a
sufficient pass band (of the order of 2 Mc) and a gain of
around 15 times is connected to the anode grid of the video
amplifier.
To decrease the shunting action of the last stages, a
video pulse from the video amplifier is fed to the cathode
follower which comprises the second half of tube L3-70 from
the load of which (R3-28) a signal is applied to the matching
circuit. The amplitude characteristic of the video amplifier,
taken from the output of the eathode follower, is depicted in
Fig. 80.
30. Construction of the Receiver
The i-f amplifier is made in the form of two subpanels:
i-f preamplifier subpanel (Fig. 81, 82), and i-f amplifier
subpanel (Fig. 83s 84).
The i-f preamplifier subpanel is located in the receiver-
transmitter unit, and the i-f amplifier subpanel, in the range unit.
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Such a separation is made because the i-f amplifier must
be placed in direct proximity to the crystal mixer to obtain
a maximum signal-to-noise ratio. But because the receiver-
transmitter unit where the crystal mixer is located is small
SPN 190 and it is not possible to put the i-f amplifier into it, the i-f
amplifier is structurally divided into two subpanels: the
pre- and the main i-f amplifier.
The pre- and main i-f amplifiers are connected to each
other by h-f cable RK-1561 which consists of two parts connected
to each other be a hermetically sealed h-f plug.
The i-f amplifier and i-f preamplifiersubpanels-are attached
to thetthasads of the corresponding units by screws.
The input of the main i-f amplifier is made in the form
of an h-f plug which is located at one end of the back edge
of the subpanel, and leads to the front panel of the range unit.
The i-f preamplifier subpanel is supplied by a power
supply cable.
The i-f amplifier power supply cable is teadnated by
seven-contact plug Sh3-1.
KTO type reference capacitors, which are connected to the
chassis by means of nuts, are used in other circuits. These
capacitors also serve as reference points for the rest of the
components connected to them.
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SPN 191
50X1 -HUM
The screws for tuning the h-f circuits are inserted in the
side of the tubes. The adopted construction of the circuits
and their attachment to the chassis provide for tuning i-f
amplifiers with the lids cloded.
The tuning screws are attached by special springs, and
after tuning are sealed with colored laquer.
To improve the operating stability of the i-f amplifier
the points of connection of the lids with the chassis are fitted
with a gasket of special high-frequency electrical seal in
the form of a special type of cord spliced with wire and a
Monel metal strip, which improves the contact between the
lis and the chassis.
The i-f preamplifier and. i-f amplifier chassis are silver platet.
A special contact rack, which shorts the power lines of the
last stages halfway to the first, is set in the middle of the
subpanel to prevent galvanic connection of the first stage
of the main i-f amplifier with the last.
The tube sereenst besides their basic function as shields,
perform the role of tube holders, which is accomplished by
special clamp springs which are part of the screen.
These springs, besides this, provide for reliable contact
between the tube leads and the panel jacks.
A view of the i-f preamplifier and amplifier from the
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50X1-HUM
mounting side are shown in Fig. 82 and Fig. 84.
31. Noise AGC of the Roiceiver (Noise AGO
A constant voltage of set noises flows from the output
cathode follower of the receiver to the coincidence tubes
and then to the amplifier, peak detector, and the output tube
SPN 192
of the automatic locking device.
The sensitivity of the automatic locking device is
controlled at a definite noise level. When the environmental
conditions or the supply voltages are altered, and also
when the tube and component parameters change as a result of
age, the level of receiver set noises may change.
An increase of noises may result in operation of the
automatic locking device.
Such a false lock causes range-only radar to be completely
faulty, since it excludes the possibility of locking on a
target.
A decrease in the noise level is less dangerous; it
leads to a certain loss of sensitivity of the automatic locking
device. ?For example, a twofold decrease in the noise level
relative to the initial level at which the automatic locking
device was set results in a loss of approximately 3-5 db in the
set sensitivity.
In connection with this a noise AGC circuit, the purpose of
which is to maintain the constant noise level at the receiver
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50X1-HUM
output when possible destabilizing factors act, is introduced
Into range-only radar.
Besides this basic requirement the AGC system must be
relatively insensitive to external interference and target
pulses whose intensity can change over a wide
range.
SPN 196 The noise ACC circuit, comprising tubes L3-9 (6n2P),
L3-11b (6N3P), and L3-10a (6N3P) is shown in Fig. 85.
The first stage (L3-9) is an ordinary amplifier stage with
resistors; the second stage (tube L3-11b) is a diode detector;
the third stage (tube (L3-10z) is a cathode follower.
The circuit operates in the following manner:
Noise from the receiver output is applied to the input of
the amplifier stage (tube (L3-9) through capacitor 03-36.
The amplified and phase-shifted noises are taken from resistca?
R3-421 which is the plate load of L3-91 and fed to L3-11b. The
detected negative noise voltage then flows from the plata load
R3-42 of tube L3-11b to the grid of cathode follower 13-10a
and thence to thegrids of the i-f amplifier control tubes.
In order to avoid the effects of pulse noises reflected
from ground objects on the ACC circuit, the latter is blocked
for a period of 50 70 microseconds from the moment of emission
of the main pulse.
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SPN 197
Nee
SECRET
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The trigger pulse from unit 2 passes to diode L3-20b (right
half), is expanded by the R3-98;C3-70 network, passes through
capacitor C3-69 to the pentode grid of tube L3-9, and blocks
the tube for a period of 50 to 70 microseconds.
Consequently, the noise AGC circuit does not function for
a period of 50 to 70 microseconds during reception (see Fig. 86).
The original noise level at the output of the receiver channel
is set by potentiometer R3-45 and corresponds to a certain negative
voltage at the AGC output.
The noise level at the output of the receiver channel is
set within limits of 5 i 7 v (0.5 of the cutoff limit).
When the noise level at the output of the receiver changes
relative to the originally prescribed level, the AGC circuit
changes its negative output voltage, leading to a change - in
the gain of the receiver and to the retention of the prescribed
noise level at the output of the receiver channel.
In the event of the absence of manipulation of the circuit
by a negative pulse when pulses reflected from ground objects
are present, the AGC circuit increases the controlling voltage,
which decreases boti" the noise level at the output of the
receiver as well as the sensitivity of the set.
32. Pulse Automatic Gain Control of the Receiver (Pulse AG
Pulse attomatic gain control id designed to maintain the
pulse amplitude of the target at the receiver output at an
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Noe
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50X1-HUM
approximately constant level when the intensity of the reflected
signal at the input changes over a wide range. This is achieved
by increasing the accuracy of determining the range to the target,
since in the absence of such control the determined range
would depend on the intensity of the reflected signal; thus,
the range would be different for two aircraft (targets) of
different size located exactly the same distance from the
SRN 202 receiver. There would also be an error in closing with the
target. This is explained in Fig. e7.
The pulse AGC circuit operates only on the basis of a selective
pulse; that is, a pulse which is locked on by the range unit.
Such selection is necessary so that a decrease in the gain of
the receiver does not occur in the presence of strong
extraneous pulses (for example, noises reflected from nearby
aircraft of the ground), which could lead to the impossibility
of locking on a weak useful pulse reflected from the target.
The pulse AGC circuit (Fig. 88) operates ?in the following
manner:
A positive pulse passes from the anode of the amplifier of
the automatic lacking device (L3-19, right half of the tube)
through spacing capacitor C3-65 to the ti-id of the amplifier
of tube L3-11 (6N1P). The performance of this amplifier (bias)
is determined by the control "Pulse Amplitude" (potentiometer
R3-65).
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"PN 202
New
A negative pulse taken from load R3-52 is detected by the
normally closed right diode of tube L3-10 and, from its load
and the stretching capacitance (R5-47, C3-39), is applied in
the form of a d-c voltage to the grid of the cathode follower
(left triode of tube L3-10) and thence to the control grids of
the i-f amplifier control tubes.
The change in bias at the control grid of tube 1.3-11a
leads to a change in the amplitude of the video pulse at the
output of the receiver channel. The magnitude of the
amplitude at the output of the receiver channel is usually
maintained to within 0.9 of the cutoff level.
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SPN
203
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VII. POWER SUI,PLY RB6-4
33. Function
This unit is intended to supply the units of the "Kvant4 rang-
only radar with rectified, stabilized voltages of:
+ 300 v, + 200 v, + 150 v, and - 150 v.
3h. Functional Diagram
The functional diagram of the power supply consists of seven
basic assemblies and is shown in figure 89.
When a -s? 115 v, 400 cps voltage is applied to the primary wir
of the transformers, voltages are taken from the secondary windinfs
and fed to rectifiers designed as bridge circuits with c-:.ystal dirdea
type D7Zh. After this, the rectified pulsating voltages are fed to
electronic voltage stabilizers.
The constant voltaues are fed from the output of these atabilizeru
to the plug connector of the unit.
35. Schematic Diagram of the Unit
A schematic diagram of the unit is shown in figure 90. The unit
is supplied by a ", 115 v, 400 cps a-c voltage.
fiectifier and Stabilizer, + 300 v
The rectifier which supplies the electronic stabilizer with
+ 300 v is built on a bridge circuit with crystal diodes D7-Zh.
SPN
204 Four crystal diodes are connected to each arm of tl-e bridge.
In order to decrease the pulsations of the rectified voitage, a
capacitor 04-1 equal to 2 microfarads is placed at the output of the
rectifier.
The circuit operates in the following manner.
When an a-c voltage (^, 115 v, )400 cps) is applied to the primar7
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OUA I -num
winding of the transformer, a voltage of .N,390 v is taken from the
secondary winding 3-5 and applied to the bridge.
When terminal 3 of secondary winding 3-5 of transformer Tr4-2 is
positive with respect to terminal 5, D4-17, D4-18, D4-19, 0/4-20 and
D4-25, Dh-26, D4-27, and D4-28 function.
At the next moment, when terminal 5 of the secondary winding is
positive, arms D4-16, D-15, D4-14, D4-13 and D4-24, Db-23, Dh-22,
and D4-21 function.
Thus, the rectified current passes through the load through both
half periods in one direction.
There are no filters in this rectifier. This is explained by the
fact that the property of the electron-ion voltage stabilizer circuit
is used as a filter.
Stabilizers of this type have instantaneous reaction to changes
in the voltage of an external power supply, which is the rectifier,
while maintaining at the same time a steady output voltage.
SPN
Further, the rectified voltage is applied to an electronic VOI.
Nur tage stabilizer which is designed as a series-connected circuit with
a control tube (L4-1) type 6P1P and a two-stage d-c amplifier (tube
L4-4) (6N2P), with a reference voltage supplied by voltage stabilizer
SG3S (L4-10), which is common for all electronic stabilizers of tie
unit.
Let us assume that, due to an increase in voltage of the ,^?? 11.5 v
400 cps supoly network, or as a result of a decrease in current cpn-
sumption, the voltage at the output of the electron-ion stabilizer
increases. This leads to an increase in the divider current, consis-
ting of resistors Rh-6, R4-7, Rh-8, and Rh-9, to a decrease in neva-
tive bias at the control grid of the right half of tube Lh-2, and,
accordingly, to an increase in its anode current and a drop in voitaR-3
across resistor R4-5. In turn, the increased voltage drop at resistor
R4-5 causes a decrease in negative bias in the left half of tube 11-2
and an increase in its anode current, and, accordingly, to an increas,3
in the voltage drop across resistor Rh-h. The voltage drop at re.,-isto
Rh-h is in no way different than the bias of control tube Lb-1, wlich
determines its internal resistance.
The internal resistance of tube Lb-1 increases, causing an 1.-)
crease in the value of the voltage applied to it and a decrease i-,th
voltage at the output of the stabilizer.
.195-
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sEcnr,T
Awl.?
SPN
206
SPN
50X1 -HUM
Thus, the resulting increase in voltage will be comoensated.
a decrease in the voltage of the ^,115v, 400 cps supply network, or
with an increase in current consumption, the voltage at the outpu-; of
the electronic stabilizer will be stabilized in a similar manner.
Resistors R4-2 and 114-88 serve to limit the current through -;ube
L4-1 (6P1P).
Capacitor C4-2 serves to increase filtering of the output voL.taw.
Capacitor C4-3 is a decoupling capacitor.
Fuse Pr4-2 serves to protect tubes L4-1 and L4-2 and transfo7mer
Tr4-1.
Rectifiers and Stabilizers, + 200 v and + 150 v
The rectifier whAch supplies the + 200 v and + 150 v electrode
stabilizers is assembled in a bridge circuit with crystal diodes 1(4ft.
Three crystal diodes are connected to each arm.
The principle of operation of the rectifier is analogous to ;hat
described above.
The 200 v electron-ion voltage stabilizer uses tubes L14-3,
and L4-5a.
The 150 v electron-ion voltage stabilizer uses tubes L4-61 114-1,
and L4-5b.
207 Rectifier and Stabilizer, - 1502
The rectifier which supplies the - 150 v electronic stabiliar ii
also designed as a bridge circuit with D7Zh crystal diodes.'Iach arm
is connected to 2 diodes.
Unlike the positive voltage rectifiers examined above, the va-
tage for the stabilizer is taken from the "minus" side of the briige
circuit in this case.
Tube L4-8 is used as a regulating tube, L4-9 as a control tube,
and L4-10 as the refe:5.ence voltage source.
The principle of operation and functions of the individual Ole-
_196-
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50X1 -HUM
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50X1-HUM
ments of the circuit are analogouz to the above-described oircuitr
with only one exception -- in the negative-voltage electron-ion stabi-
lizer, a decrease in supply voltage causes a decrease in negative Dias
as the control tube.
Resistor R4-32 is the load resistance of voltage stabilizer L14-1C.
Capacitor C4-11 serves to decrease pulsations of the voltage sta-
bilizer as well as possible self-excitations of the circuit.
SPN
208 36. Construction of the Unit
The power supply unit is built in a separate mounting rame
having a shock-absorbing frame and housing.
A general view of the unit is given in figures 91, 92, Y3, and 9L.
The more intense sources of heat, namely tubes 6P1P (6 tubes),
6N2P (3 tubes), SG3S (1 tube), and the vitrified resistor are placed
a section adjacent to the front panel. The capacitors are scpara-;ed
from the forward section by an insulating partition.
On the front panel of the unit (fig. 91) is a fuse box and a
cable with a 9-pin connector plug.
At the rear well of the unit (fig. 91) on a brace are the crista::_
diodes, which are separated from the capacitor section by another
screen made of textolite.
Also on the rear wall of the unit are the control units for
300 v, 4 200 v, 4, 150 v, and - 150 v.
The shock-mounted frame is mounted to the housing with the
locator pins and two knurled hinge nuts.
The dimensions of the unit are: 284 X 150 X 168 mm.
Weight of the unit: 4 kg.
SPN
212 VIII. Speed Unit RB6-5
37. Function
This unit is designed to automatically determine the relative
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50X1 -HUM
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SECR2T
50X1-HUM
'Oar'
speed of the target and to feed the corresponding voltage to the sight
computer ASP-NM and to the comparator unit K-8.
38. Basic Technical Data of the Unit
a. Aule for speed voltage output in mode "A":
U (v) = - 0.1 V m/sec
sp
in mode "B":
U (v) = - 0.04 V m/sec
Speed is positive during approach.
b. Maximum statistical error in determining speed:
in mode "A" -- no greater than t 10 m/sec
C.
- 100 sec to + 400 m/sec.
d. Dimensions of the unit: 92 X 92 X 170
e. Weight of the unit: 1.4 kg.
in mode
irB tl
-- no greater than t 35 m/sec
Target speed voltage is Presented in a speed range from
39. Functional Diagram of the Speed Unit (Fig. 95)
The range voltage lid from unit RB6-3, taken from cathode fol. ow
through filter R!;-13, C5-9, is applied to differentiating
circuit C5-11 R5-1.
5PN
21)4 A voltage appears at the output of the differentiating circuLt
which is proportional to the rate of change of the voltage at the
input of the circuit. Iince a range voltage is applied to the inout,
the output will provide a voltage which is proportional to rate
approach or withdrawal of the target (fig. 96).
The magnitude of this voltage is small and must be amplified to
the required value. Since the speed voltage is constant or changes
slowly, a d-c amplifier must be used for this purpose.
_ 202 -
50X1-HUM
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50X1 -HUM
4\se
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';;YPTIT
50X1 -HUM
The presence of drift makes it impossible to use ordinary d--
amplifier circuits, and, therefore, a special amplifier was designed.
The amplifier consists of a balance converter based on tubes
L5-1 and L5-2 (type 636B), a phase detector based on tube
and a cathode follower -- tube L5-4, type 6s6B.
The amplifier encompasses a feedback circuit which increases its
operating stability and provides a constant amplification factor. Th
value of this amplification factor is determined by the feedback -i
cult and is equal to 8.
The speed voltage passes from the output of the phase detect-Dr
through cathode follower L5-4 to the sight computer ASP-NN nd t-1 th
comparator unit K-8.
SPN
216 Capacitor C5-8 is used to smooth speed voltage fluctuations.
During the setup time of the speed voltage, equal to I second, caoaci-
tor C5-8 is disconnected. If this were not the case, the setup Valle
would be considerably greater.
SPM
40. Description of Schematic Diagram (Fig. 97)
A voltage proportional to the range to the target is aoplied
through filter R5-13 arvi C5-9 to the differentiating circuit C5-I and
R5-1, at the output of which is produced a voltage proportional tD th
speed of the target. TI-C,s may be explained by the fact that, at the
output of such a circuit, the voltage is expressed by the relationshiIt
o:
ILJI in
out. - ? RC
ct-E
This condition will be satisfied within a time correspondinf to
(3 + 4) RC (fig. 96) ; since, when the station is operating in moCe
U in. = 95 w 1)
20 ; then,
a ti in. _ 1 el Zi .
_
.?ca.-- - 20 cit '
correspondingly: 1
U out. = 20 RC cl 1)
dt. .
-
217 Since: RC = 1.106.0.25.106 = 0.25 sec,
LI1 Cl5)
out. - 'Mat
-204-
,!XCLET 50X1 -HUM
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, e
. 'Tr.
Fur.,7 : -
1_
?,)u.n7',
1
e.115 v
2
,115 v
3
+ 27 v
4
II
5
range
,
l_dfAle
+ 200 v
7
lock-On
(-.1 rr,ni t
8
speod
zero
9
speed
zero
10
track.
11
ilsoeed
12
13
- 150 v
14
is.
16
17
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Sv(TRFT
C&-2 c-3 c5- R5-4
0.citif 0.0114 33oopc ri 390 NO..
TrE -2
R5-2 RG-3
11(?t1 5'101.
Tr 51
c f3
-05-77.7r
L5-2 LEr-3
6S6B 6Zhie L C5-6
Zpf
R5-.73
5lo Ka
too kn.
R5-12
r RS-9 II I /Af
374?K-CL (35.vz,
Ka 1-15fia
L S14-
6S4B
R5-7
-t-TKrt
R5- RS-6
12. Ka toOKf1.
Key o 4j'e 9T,
50X1-HUM
Pos. GOST-VTU
desig. specs.
Designation and
type
Rating
No.
R5-1 VP4675006
R5-2 ozho467003Tu
R5-3 ozh0467o03Tu
R5-4 ozho467003Tu
R5-5 vP4675oo4
R5-6 vP4675oo4
R5-7 ozho467oo3Tu
a5-8 ozho467003Tu
R5-9 ozho467003Tu
115-lo ozho467003Tu
R5-11 ozho467003Tu
R5-12 ozh04670o3Tu
c5-1 uBo461o15Tu
C5-2 uB0462017Tu
C5-3 uBo462o17Tu
c5-4 uBo462o17Tu
c5-5 OZh0462022TU
OZh0462022T1J
OZh0462022TU
02110462022TU
OZhO (?)
UTU0131655
UTU0131655
UTU0131655
UTU0131655
(?)
GYa4714034
G(?)-8?0-000
Y111/16121
R5-2 Yu171F121
c5-6
C5-7
C5-8
C5-.9
L5-1
L5-2
L5-3
L5-4
R5-13
Tr5-1
Tr5-2
:; -1
SEC LT
Res.PTU-1-17_11t 15 1 MO. 1
Iies.LT-0.5-100k.A,-II-3 100 kft 1
51 kn. 1
Res.YIT-0.5-390kft-II-B 390 kft 1
Res.PTU-0.5-12kat
12 ka
Res.PTU-0.5-100katl% 100 krt 1
1
Res.MLT-1-33kft-11-13 33 kft 1
Res.LT-0.5-510ka-II-B 510 ka 1
Res.MLT-0.5-5.6kft-II-B 5.6 MI
Res.4LT-0.5-16ka-II-B 16
Res.MLT-1-51k1-II-B Si kc
2es.MLT-0.5-100kft-II-B 100 MI
Cap.MPG-P-250-0.25-I 0.25 rf
Cap.BGM-T-1-0.01f-I 0,01 plf
Cap.BGM-T-1-0.01f-II 0.01 p...f
Cap.BGN-T-1-3300pf-II 3300 pf
Cap.MBGP-1-200-A-0.5,.f-I I 0.5 frif
Cap.MBGP-1-200-A-2-II 2 pi*
Cap.MBGP-2-200-A-1-II 1 pf
Cap.MBGP-2-400-A-0.5-II 0.5 mf
Cap.BGM-2-400-(?) (?)
Radiotube 6S6B
Hadiotube 656B
2adiotube 6Zh1B
Radiotube 6S6B
Res. (?) 36 kfl
Transf. (?anode cur?)
Transformer
e.Lay L2
Relay AS1-2
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50X1-HUM
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
SECRET
gP5
218 Since the amplification remains as before, the speed scale ir
the "B" mode will equal:
50X1-HUM
The given value of sneed is determined by the relationship:
ia
sr). - TOdLt
This also explains the need for an amplifier with an amplifleaticv,
factor
sp.
8.
llout. =
When the station is operating in mode "B"
Accordingly:
U1= 195 -
510
U in. 1 cii)
at 50 sit
out. -
1
RC
q0
Since the time constant has not changed,
RC = 0.25 microfarad
1 clS)
Li out. = 200 8..t.
1.) Frp.
? 8
U out.
U so. = Uout,E ? 0.o14 v
An L-shaped filter AC is introduced for the purpose of elimi-
nating extraneous influences found in the range voltage.
The computing circuit is also a d-c amplifier with an amolifica-
tion factor equal to 8.
The necessity of obtaining a linear characteristic and stable
operation of the amplifier led to the use of a converter at the output
of circuit L5-1 and L5-2 to convert the d-c voltage to 400 cos signals
and to the realization of a basic gain in alternating current. '3uOse-
quent reverse conversion is accomplished by a phase detector
In the search mode the control grid of L5-1 of the balance col-
verter is connected to ground and the voltage at the grid is equal to
- 207 -
SECRET , 50X1-HUM
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SPN
220
50X1 -HUM
zero. The latter is also the case when locking on a stationary t4r-
get, when the range voltage does not change.
The voltage at L5-2 is also equal to zero, while the currents
flowing through the right and left windings of pulse transformer
are equal in value. There is no a-c voltage at the output wirdin7 of
Try- 2.
An a-c voltage (100 v, 400 cps) is applied to the screen grid of
phase detector from a special winding of transformer Tr-1. Durinr th.
positive half of the voltage cycle at the screen, the tube opens and
current flows through the anode circuit. During the negative cyce,
the tube is closed and current ceases to flow.
Capacitor C5-6 smooths the voltage pulsations at the anode, rhe
operating conditions of the tube are selected in the given ease so
that the voltage at the anode of L5-3 is equal to zero (this is nossi-
ble since the cathode of b5-3 is supplied by the - 100 v source).
This voltage is applied to the grid of cathode follower 1,54. A nero
voltage is fed from the output of L5-4 through feedback livider
R5-5, and R6-6 to the grid of L5-2 and to the sight circuits.
When tracking an approaching target the range voltage increaues.
The derivative of this increasing value is positive and, therefore,
the voltage at the left grid of the balancing amplifier increases to a
certain positive value. This value will depend on the closing so ted.
Due to the increase in voltage at the grid, the current in toe
L5-1 increases in comparison with the current in the right half. Clive
currents cease to compensate for each other and an a-c signal appears
at the output of Tr-2. the middle point of Tr5-2 is supplied by an
a-c voltage (200 vl 400 cps) from transformer Tr-l. The a-c voltare
from the output of Tr-2 is applied to the grid of phase detector
SPN
222 As may be seen from figure 96, the phases of the signal voltae
and the voltage at the screen grid of L5-3 are, in this case, in
opposition. This leads to the fact that, during the positive half of
the screen voltage cycle, the voltage at the control grid decreascr;
and the anode current of the tube also becomes less, while the voltage
at the anode increases.
The increase in voltage at the anode is transmitted through Li:-3
to the sight. In tracking a receding target the voltage at the con-
trol grid of L5-1 is negative and the phase of the signal voltage at
L5-3 coincides with the phase of the reference voltage.
50X1-HUM
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QUA] -I-1 U IVI
Nor
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bZWILE
50X1-HUM
The anode current of L5-3 increases and the voltage at the cnodf
and at the output of the circuit drop. The values of the voltaga at
the output become negative. In order to obtain a linear transfer
characteristic, the entire circuit encompasses a feedback circuit in
the form of divider R5-6, R5-5, and R6-6.
Due to the high "internal" gain, the transfer constant of tfe
entire amplifier is determined in the basic feedback circuit by:
-
1 + K A
where: K - the transfer constant of the amplifier with feedback;
Ko the transfer constant of the same amplifier without a
feedback circuit;
the feedback factor.
In our case Ko Pt', 1,000.
223 )3 = R5-5 4- a6-6
1-6-4 + R6-6 15-5 -6"
SPN
Thus:
1,000
1,000 8
8
Since the scale (slope of the characteristic) of the speed vol-
tage depends on the value of the transfer constant, it may be cortrolild
by changingA by means of R6-6.
Null control is accomplished with the aid of variable resistor
R6-10, which balances the currents in L5-1 and L5-2.
To decrease speed voltage fluctuations, which will occur because
of fluctuations in range voltage, the smoothing filter 15-6 and c:&
is introduced into the feedback circuit.
The principle of operation of the filter is based on the fact
that, in the given case, the feedback factor for the high-frequency
components of speed voltage will be considerably greater than 8, ;ince
the equivalent resistance of C5-6 will decrease with an increase tn
frequency and will become less than R5-6.
Accordingly, the amplification factor of the amplifier for high-
frequency components decreases and fluctuations do not pass to the
_210-
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50X1-HUM
output of the circuit.
A delay in switching on the filter is necessary in order to ee-
crease the setup time of the speed voltage.
SPN
.224 In the differentiating circuit RC = 0.25 sec. Without consirer-
ing the filter, the setup time is 0.75 4 1 sec., and with the filter
it reaches greater values (RC of the filter = 0.05; 4RC = 0.2 sec,
considering gain, RCequiv.= 8 x 0.2 = 1.6 sec).
In the search mode a search voltage will appear at the input of
the differentiating circuitwhidh will fluctuate between 25 and 18
volts. When locking-on is achieved, the voltage will correspond to
the range to the target.
In order that the unit will not be overloaded by large voltaies
while in the search mode (scanning rate:t. 3,000 m/sec), the grid cir-
cuit of the input tube of the balance converter L5-1 is connected to
ground by contacts 1;2 of relay R5-1 and opens only at the moment of
lock-on, while, simultaneously, contacts 3;4 of the same relay serd
a lock-on signal to the sight ASP-5NM.
41. Construction
The speed unit has a cylindrical shape with a maximum diameter 01
92 rmm] and a length of 170 rim). The unit is dust- and moisture--
proof.
Located on the front panel of the unit are tubes with rubber
SPN seals protected a perforated metal casing, and the connecting cab.:_e
225 with hermetically sealed bushings located under the protective face
plate and shield. (Fig. 99).
Perpendicular to the front panel is the mounting frame which as
cutouts of complex shape.
On the top of the mounting frame (fig. 100) are located the
power transformer, a type PSN relay, an interstage transformer
TI-87-0-000, type LOP capacitors, type MPOP capacitor for the dif-
ferentiating circuit, arid a wiring panel.
Precision resistors are located on the bottom of the mounting
frame (fig. 101).
The unit has a cylindrical housing with a sealing flange.
- 211-
top%
SECRY3T 50X1-HUM
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50X1-HUM
Sealing is acconplished through the use of a rubber gasket 1e-
ween the front panel. and the flange of the housing. The unit hes
removable holding straps.
The weight of the unit is 1.4 kg.
SPN
228 4. Control Panel (K-6)
42. Function of Control Panel
The control panel is the center of all the basic controls of the
set and is the control point from which is measured the voltage aL th
"sensitivity" Potentiometer of the automatic lock-on device. In Adi-
tion, the "time relay" which serves to delay cutting in of the h.1411
voltage in unit RB6-2M, and the circuit sidtching relay for the 01:Pra-
ting modes of the set are also located on the control panel.
43. Schematic Diagram of Control Panel
A schematic diagram of the control panel is given in firure 102.
Fuse PR6-2 (5 a) it located in the 115 v, 400 cps circuit-breaker.
When the current consumed by the sight or the radar in the 115 v,
400 cps circuit exceeds 5 amperes, fuse PR6-2 blows the circuit-break-
er in the network.
Fuse PR6-1 (10 a) is located at the breaker for the 27 v cirruit.
When radar or sight current exceeds 10 amperes in this circuit, ft:se
PR6-1 breaks the circuit.
The "AFC Gain" potentiometer serves to regulate the initial tias
at the control grid of the i-f amplifier tube of the AFC circuit.
Capacitor C6-2 blocks high-frequency current from resistor 6-3.
SPN
229 The "Sensitivity" notentiometer R6-13 and resistors 16-L2 an6
R6-14 create the necessary level at which the automatic lock-on cir-
cuits begin to operate (see the description of the automatic Lock--)n
circuit of range unit iBo-3).
The "Range Zero" potentiometer (E6-15) and resistor R6-1.6 coft-ris,
a divider from which is taken the voltage for regulating ran;',. zer- in
the "Fast Sawtooth" generator.
Potentiometer R6-11 is located in the grid control circuit of the
SECRET 50X1-HUM
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aVXHET
50X1 -HUM
fast sawtooth generator and regulates the range "Scale" in mode MP,
Potentiometer R6-17 regulates the range "Scale" in mode "B".
'Potentiometer R6-6 is located in the feedback network of tht
cult which provides the speed voltage and serves to regulate the
"Speed Scale."
Potentiometer A6-10, resistors R6-8, R6-9, and capacitors Ot-3,
C6-4 are placed in the cathode circuits of the amplifier used in the
speed processing circuit. Potentiometer R6-10 regulates the speed
"zero."
The purpose of relays R6-1 and R6-2 is to delay cutting in cf
high voltage for the period of time necessary to warm-up the modtlator
in the receiver-transmitter unit. Relay R6-1 is a thernorelay; 16-2 1
an electromagnetic relay.
SPN A voltage of + 27 v is fed to the winding of R6-2, which closes
230 the high-voltage circuit (contacts 7-12), through the normally open
contacts of relay 16-1 (contacts 3-4).
When the toggle-swi_tch "stantsiya" feet] on the sight is switchei
on, a voltage (-4115 v, h00 cps) is applied to unit RB6-4, where bhe
supply voltages of the set are Produced. A - 150 v voltage is fe-i to
thermorelay R6-1. The operating time of the thermorelay is ;.5 t
3 min. When the relay operates, contacts 3-4 close and + 21 v is
applied to the winding of relay R6-2, operating this relay and 01.-)sin
contacts 7-12.
After this, the high voltage may be turned on by means of te-gle-
switch "Radio-Optics" located on the control panel of the sight. plheI
this switch is turned on, a voltage of e. 115 v, 400 Cps is anpli,d t)
the primary winding of the high-voltage transformer in unit i.66-?
and signals that the high voltage is on.
Fuse P116-3 (0.5 a) is located in the high-voltage switching
cult. If If current consumption in this circuit exceeds 0.5 annere,
the fuse blows and the circuit is opened.
Relay 116-3 serves to switch the radar circuits between nodes
"A" and "B". In mode "A", when the relay is de-energized, the rangt,e
voltage is applied to the Sight according to the rule:
1-)
. 195 -
(contacts 11 11 and 6), the circuit 6-17, R6-18, R6-19 is 3horted (con-
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tacts 9-1), and the ferrite switch switches operation of the antenna
to wide beam (contacts 12-8 and 10-3).
SPN
231 With the presence of a mode "B" signal, relay 116-3 operates and
disconnects the range voltage from the sight circuits, applying it to
unit K-8 (contacts 11-5). The network 116-17; R6-18; 116-19 is corriec-
ted in series with the notentiometer "Range Scale A," fcllowing tie
rule:
U 195 _ 50
Simultaneously, the ferrite switch switches the antenna to
narrow beam. Resistor A6-21 (100 ohms)serves to measure the cur mts
of the ferrite switch in moth modes.
Resistors R6-7 and 116-20 provide the required magnetization
current for the ferrite in both modes.
44. Construction of Control ?anel
(Figures 103, 104)
The control panel is made of a box chassis and a housill- whi-h i3
fastened to the chassis by 5 screws. On the front Panel of the ulit
are the following:
a. "Sensitivity" potentiometer
SPN b. "Range Zero" potentiometer
232 c. "Range Scale A" potentiometer
d. "Range Scale B" potentiometer
e. "AFC Gain" potentiometer
f. "Speed Zero" potentiometer
g. "Sneed Scale" potentiometer
h. "115 v, 5 a" fuse
i. 115 vl "V.N." (High-Voltage], O. a fuse
j. "27 v", 10 a fuse
At the bottom of the unit is a cable Which connects to an in-;er-
mediate cable with the aid of a type "R" connector with 28 contacts.
Dimensions of the unit: 170 X 110 X 78 mm.
0/eight of the unit: 1.5 kg.
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SPN
235 X. Comparator Unit (K-8)
45. 2unction
The comparator is designed for:
SPN
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a) Supplying a present-range-to-target voltage to the pilot's
range indicator "UD-1" following the rule:
0 range (volts) = 3.75 D (km).
b) Automatically comparing present range to target with the per-
missible launch range of homing missiles K-13 and supplying a trLgge,,,
signal to the green light "Launch" located on the pilot's instrument
panel.
c) Signalling When withdrawal-from-attack range has been re,achell
(the red light "Pull-Out" located on the pilot's instrument pane4.
d) Feeding a d-c voltage (4- 27 v) to VRD-2A.
Switching the circuits of the unit to operating status is acom-
plished automatically by lock-on and mode signals.
46. Basic Technical Data of the Unit
a) The operating range supplied to the pilot's range indica;or
"UD-1": 0 4. 8 km.
b) The relationship of present-range-to-target voltages sup)liel
to the pilot's range indicator is given in table #1.
Table #1
236 D rrange] (m) 1.14 (v)
a
1,000 3.75
2,000 7.50
3,000 11.25
h,000 15.00
5,000 18.75
6,000 22.50
7,000 26.25
P,000 30.00
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SPN
237
c) The relationship of withdrawal-from-attack si2nal
signal) to range-to-target:
1,000 in Dpull- out 4 ,in
d) Dimensions of the unit: 159 X 109 X 90 [mm].
e) Weight of the unit: 1 kg.
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47. Description of Operation of Unit According to
Functional Diagram
A functional diagram of the unit is given in figure 105.
The permissible range voltage (lJa per from the out)ut of VR:)-2A
and the present range voltage (LU- 195 - P ) are fed through the
-35
cathode follower to the comparator tube L8-2, which is closed in the
initial state.
The moment of launching the missile is determined from the
equality:
When Uj
01ores 4 Dner
pres Der/
tube L8-2 opens and the voltage at itf
Uci
anode drops suddenly. At the same time, the voltage at the grid ff
the tube of relay L6-38 decreases, the tube closes, and the relay,
which is connected to the anode of the tube by its normally close
contacts, turns on the green light "Launch."
The "pull-out" circuit consists of a precision divider to which
is fed, on the one hand, the present range voltage and, on the otter,
a negative voltage of - 150 v.
The voltage from the divider is applied to the grid of tube
L8-3b, to the anode of which is connected the pull-out signal rely.
The tube is closed in its initial state.
With the arrival of a lock-on signal and when the range voltage
has reached a value equal to a distance of 1,000 4.1,150 in, the tube
opens and the relay operates. The "Pull-Out" light on the pilot's
instrument panel turns on.
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SPICRET
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3.
0
tio Go NI 0
I
r6 03 ?I.
a? N
E 4 ?I ?-9
0
l../
2
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The circuit used to convert the present range voltage to the vol-
tage which is applied to the pilot's range indicator consists of an
operational amplifier in a negative feedback circuit.
The present range voltage, which is applied to the input of :he
operational amplifier, changes from 195 v to 35 v with changes in rani
from 0 to 8 km; that is, it changes according to decay law.
In connection with the fact that the full deflection current of
SPN the pilot's range indicator is equal to 10 ma and the resistance )f ti!'238 instrument is equal to 3 kilohms, it is necessary that the voltav in
the indicator change within limits of 0 to 30 v with changes in r3nge
(Dpres) from 0 to 8 km; that is, according to an increasing law.
NM"
Conversion of the law to a range voltage scale is accomplish :d b
the operational amplifier which sends a range voltage in the neceisar-
scale to the pilot's indicator.
48. Description of Operation of Unit According to
'4-thematic Diagram
A schematic diagram of the unit is given in figure 106.
When the set is operating in mode "A", relay R8-5 is in the re-
leased position. In this case the circuit of the range instrument is
open.
In the absence of a lock-on signal, relays R8-3, R8-4 are in the
released position.
The range instrument and "Launch" signal circuits are ooen and
part of the divider of the pull-out circuit is connected to grounl.
In the presence of a mode "B" signal and a lock-on signal, the
relay operates and the circuit becomes operative.
The basic function performed by the unit is the comparison er two
voltages:
W ores -- supplied by the range unit,
tentiometer VRD-2A.
and l.).1per
taken frog, po-!
The present range voltage in the scaletAj= 195 - , taker troll
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Nag,
SPN
240. unit RB6-31 flows through cathode follower L8-1 (a) to the precision
divider R8-33, R8-341 R8-35, to the other end of which flows (ale(
through the cathode follower L8-1 (b)) the permissible range voltege
taken from potentiometer VR.D-.2A. The control grid of tube L8-21 t
pentode with high transeonductance and a high-resistance anode bed,
is connected to the middle point of the divider; therefore, the sIiight-
est change in the voltage at the grid with respect to the cathode will
cause a sharp change in the potential of the anode.
SPN
Tube L8-3a is open in its normal state.
The operating condition of tube L8-2 is selected so that when
voltage Lickpres is greater or equal to L.1,1 per, the tube opens and E
voltage is suddenly applied to its anode. The drop in voltage though
divider R8-7, R8-8 is applied to the grid of tube L8-3a. The tube
closes and de-energizes relay R8-1. The green light "Launch" on -Me
pilot's instrument panel is turned on. The withdrauml-from-attaci:
circuit consists of a precision divider and tube L8-3b; the anode of
this tube is connected to relay 48-2. One side of the divider is
supplied by a voltage of - 150 v and the other side by the present
range voltage.
In its initial state, when there is no lock-on signal, part of
the divider is grounded through contacts 3 and 4 of relay Rh-Li, mid a
negative voltage from Re-13 is applied to the grid of L8-3b, closing
the tube to current flow.
With the arrival of a lock-on signal, relay R8-4 operates and
the divider is disconnected from ground.
Now a range voltage flows to the divider. 'When the range votage
equals 175 4 172 v rsic), corresponding to a range of 1,000 - 1,150
the potential at the control grid of L8-3b increases until the tnhe
opens and relay R8-2 operates. The red light "Pull-Out" on the plot'L
instrument panel is turned on.
In order to check for errors in the comparator circuit and tne
pull-out range circuit during ground checkout, a calibration signal i;
taken from the control instrument KJK. In this case, relays '6-7 and
R8-6 will operate and sEnd voltages from KPK to the input of the cm-
parator circuit, simulating permissible and current range voltages.
The circuit which supplies the range voltage to the pilot's .--anvi
indicator is designed with tubes L8-4 and L8-5. The true range voltavE
changes from 195 to 35 v; that is, the voltage drop will equal 160 v.
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The voltage applied to the range indicator must change froml v te
30 v; that is, the voltage drop to the indicator is approximete4 5
times less.
This condition determines the scale of the operational amplifier.
which is set by the ratio of the arms of divider R8-16, R8-17.
For precise adjustment of the scale, the divider is connected tc
potentiometer R8-16, the center point of which is connected to the
grid of tube L8-5.
SPN
242 The operational amolifier represents a servo system with strong
negative feedback.
Tube L8-5, a pentode with high gain, picks up the smallest
changes in voltage at the center point of potentiometer R8-16 ant,
after amplification, feeds the voltage through divider R8-20, R8e21 to
the grid of cathode follower L8-4b.
A change in voltage at the cathode of L8-4b causes a change in
the voltage drop across R8-17 so that the voltage at the center point
of potentiometer RE-16 will always equal zero. As an example, let us
assume that the voltage at the cathode of L8.L.4a decreases; then the
potential at the control grid of L8-5 decreases, the voltage at tie
anode of this tube increases and is fed through divider R8-20, RE-21
to the cathode follower L8-4b. The increase in voltage at the cathode
of L8-4b causes an increase in the voltage drop across R8-17 so teat
the voltage at the center point of potentiometer R8-16 will equal zere.
On the other hand, if the voltage at the cathode of L84La in-
creases, the voltage at the cathode of L8-4b decreases to a correspon-
ding degree and the voltage at the center point of potentiometere
R8-16 will again equal zero.
The range voltage in the necessary scale is fed to the Pilot's
range indicator.
SPN Tubes L8-6 and L8-7 form a rectifier with electronic stabilize-
243 tion for supplying VRD-2A with a d-c voltage of 28 v. Potentiometer
R8-41 (VRD), located on the front panel of the unit, sets the outeut
voltage of the rectifier.
49. Gonstruction of the Comparator
The comparator unit is built in a box chassis, one wall of welch
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forms the front panel. All parts are mounted on plates to nrovile
free access to the parts when reolacement may be necessary (fig. 107-
108).
The housing is fastened to the chassis with screws.
On the front nanel of the unit are the following:
1) "Range Zero" potentiometer (A-24).
2) "Range Scale" ontentiometer (11-16).
3) "Pull-Out" potentiometer (R-12).
L) "VRD Calibration" potentiometer (R-41).
5) six control points.
6) Two terminals: "Out. D" and "Out. VRD", which can oe uovA
to check the comparator and pull-out channels in the aircraft or in
the absence of VRD-2A.
The unit is connected to the intermediate cable of the fader with
the aid of a cable (attached to the comparator) terminated b:r a 3 -
contact plug type 2114.
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'NW
SPN
246 XI. Control instrument (KPK)
aPN
247
0. Function
The control instrument KPK is designed for measuri:Ig the bafic
parameters of the radar, controlling its circuits, checcing rangf.
calibration, accurately measuring the range voltages in bott, mos b2
the compensation method, as well as for measuring pull-out range and
and errors in the comparator circuit in unit K-8.
51. Technical Data
1. Voltage control:
a. 115 v, h00 cps (scale 300 v)
b. 27 v (scale 30 v)
4 300 v
C. (scale 300 v)
d. t 200 v (scale 300 v)
e. 1.50 v (scale 300 v)
f. - 150 v (scale 300 v)
Measurement accuracy for All scales is no less than
2. Current control:
a. Receiver crystal current (scale 3 ma)
b. AFC crystal current (scale 3 ma)
c. Magnetron current (scale 3 ma)
d. Ferrite switch current (scale 60 ma)
Measurement accuracy for all scales is no less than ! 2.5Z.
The Control Instrument Provides for:
a. Manual gain control (MGC) within limits of not less than
0 - 12 v in the "MGC" oosition of toggle-switch "AGC-PRIC".
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b. Manual frequency control (MFC) by changing the voltage in the
reflex klystron within limits of not more than 80 v and not 14s
than - 120 v in the "MFC" position of toggle-switch "MFC-AFC".
The Control Instrument Calibrates the Following Voltages by the
,ympensation Method:
a. Range voltage in mode "A" at the points: 500 m, 1,000 it,
1,500 m, 2,000 m, 2,500 m, and 3,000 m.
b. Range voltages in mode "B" at the points: 500 m, 1,000 n,
1,500 m, 2,000 m, 2,500 m, 3,000 m, 3,500 in, 4,000 m, 4,500 m, 5100 11
and 5,500 m.
Measurement accuracy is not less than ? 1 m.
52. Components of the Instrument
The following components are included in KPK:
a. The KAK instrument Proper (02.761.057.)
b. Ultrasonic calibrator UKKM-1.
c. Two connecting wires with Plugs.
d. Coaxial T-junction for connecting UKKM-1.
53. Description of the Operation of KPK According to
Ichematic Diagram (Fig. 109)
The control instrument ITK consists of two basic as8emtlies:
a. The control board, similar to RB6-PK.
b. The compensation measuring assembly.
SPN
248 Description of Schematic Diagram of Control Board
war'
The following set parameters may be checked with the aid of tie
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control board:
a. Voltage ll q v, Wo cps
b.
c. + 300 v
d. t '700 v
e. 4150v
f U -150v
g. TK I crystal current of receiver channel
h. TK II crystal current of AFC channel
1. T.M. magnetron current
j. U voltage Proportional to range
k. F.K. currents of ferrite switch
In addition, the control board provides for manual control a:
gain (MGC) and manual regulation of voltage at the klystron reoeller
in the AFC channel.
The control board circuit consists of two functional assemblies:
The assembly for measuring the parameters of the set, which in-
cludes the wafer switch "Mode" (V1-11P2N) and instrument IP-1 "Moue"
of the VA-46 type.
The assembly which provides for control of the set and consifts
of two toggle-switches "AFC-MFC" and "AGC-MGC" and two dividers, vhiok
include the "Tuning" and "Gain" potentiometers.
The parameters of the set are checked in the following manner:
SPN
249 a) In checking the ^,115 v, the voltage passes from to contacts
Sh-1 of KPK through resistors R3; R4* and crystal diode "D-1, under-
going half-wave rectification, to wafer switch V-1 (a) in loasitior
11,,, 115 v" and thence through instrument IP-1 "Mode" to V-1 (h). From
wafer switch V-1 (b) the ",%, 115 v" voltage is applied to contact 3 of
Sh-1 of KPK. Resistors a3 ani R4* are selected so that the fall scale
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SPN
250
equals 300 v.
b) The "+ 27 v" voltage is fed from contact 5Sh-1 to wafer
switch V-1 (a) in the position "4- 27 v" and through instrument IP-1 t)
V-1 (b); from the wafer switch, the "+ 27 v" measuring circuit is con-
nected to ground thro/gh resistors R14 and R15*. Resistors a4 ald
1115* are selected so that the full scale of the instrument is 30 I.
V) 11+ 300 v" is fed from contact 16 of connector Fh-1 4,o wa'er
switch V-1 (a) in the position "t 300 v" and through instrument I '-1
to V-1 (b).
From the wafer switch, the "+ 300 v" measuring circuit :is con-
nected to ground through resistors R9*, R10, and R11. These resi:3tor:
are selected so that the full scale equals 300 v.
g) "+ 200 v" is fed from contact 15 of connector Sh-1 to wa:er
switch V-1 (a) in position "+ 200 v" and through instrument 129-1 to
V-1 (b); the It 200 vfl measuring circuit is connected to ground from
V-1 (b) through R9*, R101 and R11. (300 v scale).
d) "150 v" is fed from contact "11" of connector Sh-1 to water
switch V-1 (a) in position "150" and through instrument IP-1 to
The "+ 150 v" measuring circuit is connected to ground from V-1 (1)
through R9*, R10, and R11. (4- 300 v scale).
ye) "- 150 v" is fed from contact "13" of connector Sh-1 to
wafer switch V-1 (b) in-position "- 150 v" and through instrument EP-1
to V-1 (a). From V-1 (a), the "- 150 v" measuring circuit is conrectet
to ground through R9*, 410, and R11. (- 300 v scale).
zh) "TK I" is fed from contact "8" of Sh-1 to wafer switch I1-1 (
in position "TK 1" and through instrument IP-1 to V-1 (b). rom t-1
the TK I measuring circuit is connected to ground through resistor
R-12*. This resistor is selected so that the full scale of the irstru.
ment equals 3 ma.
z) "TK II" is fed. from contact "9" of Sh-1 to wafer switch
V-1 (a) in position "TK II" and through instrument IP-1 to V-1 (b).
From V-1 (b), the TK II measuring circuit is connected to ground
through resistor. R-12*. (3 ma scale).
i) "T.M." is fed from contact "10" of Sh-1 through resistors
R-1, R-2* to wafer switch V-1 (a) in position "T,M." and through 11-
strument IP-1 to V-1 (b). The T.M. measuring circuit is connected to
ground from V-1 (b)
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UA I -nuivi
SPN
251
Resistors R-1 and R-2* are selected so that the full scale erualt
3 ma.
k) "W " passes from contact "7" of connector Sh-1 to wafer
switch V-1 (b) in position "W" and through instrument IP-1 to 1T-1 (a',
From V-1 (a), "L,4 " is fed through R5 to point + 195 v of divider 1i8,
R6*, and R7.
With a range voltage equal to * 195 v (range equal to zero), the
pointer of instrument I?-1 remains at zero. At other ranges, the in-
strument measures the range voltage in volts (150 v scale).
1) "F.K." passes from contact '16" of connector Sh-1 through re-
sistors R22* and R21 to wafer switch V-1 (b) and through instrumeut
IP-1 to V-1 (a). The current measuring circuit of the ferrite swdtch
is connected from V-1 (a) to + 27 v. Resistors R22* and R21 are feler-
ted so that the full scale equals 60 ma.
Manual Gain Control and Manual Frequency Control
Manual gain control (MGC) and manual frequency control (MFC)- are
accomplished in the following manner:
Dividers R16*, R171 R18, and 1119* are fed by - 150 v through
toggle-switches V1 and 72. The dividers are designed so that a vol-
tage regulated from - 30 to 120 v is taken from potentiometer RaY
(MFC) and a voltage regulated from 0 to - 12 v is taken from potettio*
meter H20 (MGC).
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SPN 252
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DESCRIPTION OF THE SCHEMATIC DIAGRAM OF THE COMPENSATION4MA3URIU
ASSEMBLY
The circuit of the compensation-measuring assembly consists
of four functional elements:
a) Voltage dividers R-38 i. R17, from which a voltage
proportional to the range is taken after each 500 n according
to the law:
Cr c s
1,4) L1A/
b) Voltage divider R23 -4-R37, from which a voltage proportional
to the range is taken after 500 m according to the law:
ua=
v) Voltage dividers R35, -R 46, from which a voltage
proportional to the range is taken after 500 m according to
the law:
a--Tral-(di-ffezence)
I: 3 42 j".)
g) A compensation circuit, which consists of:
KA
a. two type VA-46 "compensation" and "error" instruments.
b. switches "4'," " "011-off," 1
IC:parse-Fine . "
v. Resistors R-611 R-620 R-63, R-66, R-67, R-68.
g. "Error" potentiometer (R-64).
d. Voltage rectifier circuit for supplying the " 4ror"
potentiometer.
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SPN 253 RANGE-MEASURING CIRCUIT IN MODE "A"
A voltage proportional to the range, taken by "Range"
switch (V-46) from divider R38-R47 is applied throagli toggle
switch "On-Off" (V-8), and ?set mode" switch (V-5), located
in position "A" on "compensation" instrument (IP-3).
"Coarse-Fine" switch (V-6) is set in the "Coarse" position.
Set voltage flows simultaneously to the instrument through
the "set mode" switch in position "A" and through the "Error"
instrument (IP-2). The needle of the "Error" instrument must
remain at zero.
If the voltage taken from the divider is equal to the set
voltage, the needle of the "compensation" instrument will
also remain 0 zero.
If the voltages being compared are not equal, the unbalanced
voltage, which is set at the "Error" potentiometer, is determined
by the "Error" instrument.
Then, setting the "Coarse-Fine" switch at the "Fine" position,
we determine the exact error, with the corresponding sign, directly
by the "Error" instrument.
The "Error" instrument measures the difference in the
compared voltages fed to it.
The entire scale is 120 meters.
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SECRET
50X1-HUM
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SECRET
50X1-HUM
SPN 2,5 CIRCUIT FOR MEASURING THE PULL-OUT RANGE AND ERROR OF THE
COMPARITOR CIRCUIT IN UNIT "K-8"
The determine the pull-out range and error of the comparitor
Circuit, it is necessary to connect "Output D" and "Output VRD"
in KPK with the corresponding terminals in unit "K-8."
The "calibration" toggle switch in KPK is set in the "on?
position.
The "on-off" toggle switch is set in the "off" position.
The "set-mode" switch is set in the "0" position.
Lock on a target at a range of 1000 m, and turn on the
"pull-out" light by rotating the handle of the potentiometel
Road the exact value of the pull-out range on the scale of the
"Error" instrument.
'You -00+ 1000 m 1: D instrument.
The full scale of the instrument is 150 meters.
Having set the "set node" switch at "C" position, determine
the error of the comparator circuit in an analogous manner
according to whether the "Launch" light is lit upon locking on
a target at distances of 1,000, 2,000, 3,000, 4,000, rnd 5,000 m.
In this case, the full scale of the instrument is 120 meter.
In both the above-described measurements, the "Error"
instrument is connected in series with the present-range voltLge
circuit.
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50X1 -HUM
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SECRET
SPN 255
50X1-HUM
For fine adjustment of the VIIT divider under factory conditions,
the "set mode" switch has the technological position "N"
(adjustment).
COMPENSATION CIRCUIT
The compensation, currentless method of measuring is used
in this circuit.
It consists of the following:
A "Compensation" instrument is acted upon by two voltages:
on the one hand, the voltage taken from the divider, and on
the other, the set voltage.
If these voltages are equal, it means that no current
flows through the instrument, and its needle stays at zero.
If the needle of the instrument is deflected to one side
or the other, it means that the voltages being compared are
not equal. Then, setting the "Coarse-Fine" switch in the
",Fine" position, we switch in the error-measuring circuit.
In this case, "Error" potentiometer (R64), which is supplied
by a rectified voltage of 3.5 v, is connected between the
instrument and the voltage taken from the set.
If the voltage flowing from the set is less than the voltage
taken from the divider, then the switch with the "error" sign
must be set in the "+" position. Then the voltage taken from
the potentiometer will be added to the voltage taken from the
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50X1-HUM
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SECRET
SPN 256
50X1-HUM
set; the voltages flowing to the instrument are equalized by
changing the voltage at the potentiometer.
The voltage at the potentiometer is measured by the mError"
instrument, which is connected to the output of the "Error"
potentiometer.
For convenience in reading errors, the scale of the "Error"
instrument is graduated in such a manner that the full scale
corresponds to 30 a in mode "Ap", to 120 m in mode "ill and"C,"
and to 150 m, in mode "0."
54? CONSTRUCTION OF THE INSTRUMENT (Fig. 110, 111)
Tie control instrument is made in the form of a table model
[all control located on top].
All the elements of the circuit are located on a chassis,
which also forms the front panel of the instrument.
The instrument has a removable housing with a lid; the
lid is fastened to the housing bytwo"phonograph" type locks.
There is a handle on the Bids of the housing for convenience
in carrying.
There is a section in the housing for:
a) Ultrasonic line ULKM-1, which is fastened to the
housing by two screws;
b) a coaxial T-joint;
v) two leads with plugs;
g) A KM instrument cable;
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SECRET 50X1 -HUM
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Nor
SPN 257
SECRET
The face panel is attached to the housing by four screws.
Controls are located to the left on the face panel and.
include:
a) A type VA-46 "Mode" instruMent.
h) "Mode" wafer switch.
v) "Gain" control.
g) "Tuning" control.
d) "MGC-AGC" switch.
e) "AFC-MFC" switch.
A measuring attachment is located to the right on the face
panel and includes:
a. A type VA-46 "Compensation" instrument.
b. A type VA-46 "Error" instrument.
v. "Range" (in meters) wafer switch.
g. "Set Mode" wafer switch.
d. "On-Off" switch.
e. "Coarse-Fine" switch.
zh. "+" " " switch.
s. "Error" control.
"Calibration-On" switch.
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SECRET
50X1-HUM
50X1-HUM
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Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1-HUM
TNDEX
SPN 260
I. GENERAL INFORMATIOY
1. Application
2. Basic tactical-technical data
3. Range-only radar assembly
II. PRINCIPLE OF OPERATION AND INTERACTION OF
INDIVIDUAL ELEMENTS OF "KVANT" RADAR
4. Principle of operation
5. Block diagram of range-only radar
6. Functional diagram
III. ANTENNA-WAVEGUIDE ASSEMBLY
7. Application
8. Basic tacticalechnical data of the
antenna-waveguide channel
9. Waveguide channel
10. Description of ferrite commutator
IV. RECEIVER-TRANSMIWFR UNIT
11. Application
12. Make-up of the Unit
13. taste tactical-technical data of the unit
14. Description of the operation of the unit
according to the functional diagram.
15. Description of the operations of the unit
according to the schematic diagram
-2h2 -
7Pr
11
1 6
33
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50X1-HUM
SPN 261
a) Submodulator 42
b) Blocking Oscillator 44
v) Cathode follower
g) Modulator
d) High-voltag- rectifier i2
e) Discharge tube firing rectifier )4
16. High-frequency receiver-transmitter device
a) Function
b) High-frequency device
v) Magnetron oscillator
g) Schematic diagram of high-frequency head 'h
d) Design features of high-frequency head
17. Klystron AFC 17
18. Structural design of the unit D
V. RANGE-ONLY RADAR RTOEIVER UNIT
19. Function of unit 1 )7
20. Basic technical characteristics of the unit 1 )7
21. Description of the unit operation based to
to the functioaal diagram o
a) Search mode
b) Tracking mode
22. Description of the operation of the unit based
on schematic diagram
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50X1-HUM
INEW
SPN 262
a) Trigger multivibrator
b) Fast sawtooth generator
v) Slow sawtooth generator
g) CompPritor circuit
d) Range pulse generator
e) Time disarminator
zh) Control unit (double generator)
z) Automatic locking device
k) Constructive desigx of the unit
VI. REUEIVER
23. Purpose and nake-up
24. DescriptioT of the operation of the receiver
according to functional diagram
25. Function of if amplifier
15
13
72
72
?(1+
26. Description of if preamplifier according to
schematic diaram
27. Main if ampli_ier 1_92
29. Detector
29. Video amplifier
30. Construction HYr the receiver
31. Receiver AGC
32. Receiver puls A.GC
9PN 253
VII. POWER SUPPLY UNIT Wi6-4
33. Function
34. Functional dtq.gram
3
-244 -
S2CPET 50X1 -HUM
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Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9. /um
Iner
VIII.
35. Schematic diagram of unit
36. Construction of unit
SPEED UNIT RB6-5
37. Function
r. Basic techn_cal characteristics of the unit
39. Functional diagram of speed unit
40. D'scription a:!: schematic diagram
41. Construction
;'33
12
12
c24
IX.
COETROL BOARD (K-S)
42. Function of control board
43. Schematic diai7ram of control board
23
44. Construction of control board
31
SPN 264
X.
CONPARITCR UNIT (L-1)
45. Function
35
46. Basic technical characteristics of the unit
35
47. Description of the operation of the unit
according to runctional diagram
48. Description of the operation of the unit
according to schematic diagram
43
49. Construction of comparitor unit
43
XI.
50. Function
51. Technical data
'43
52. Components of the instruments
2 7
53. Description or KPK according to schematic diagram
54. Construction of the instrument
256
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Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1-HUM
Nomenclature of Elements
State National
Pos. Standard, VTU
Design. Normal Drawing
Name and Type
Basic
Data
Rated
R2-I USO 467 019TU Resistance ULM-0.12-220 Ohm-I 220 Ohm
R2-2 U80 467 019TU Resistance ULM-0.12-3.3 kOhm-I 3.3 kOhm
R2-3 ugo 467 019TU Resistance ULM-0.12-2.7 kOhm-I 2.7 kOhm 1
R2-4 uED 467 019TU Resistance ULM-0.12-3 kOhm-I 3 kOhm 1
R2-5 U.I 467 019TU Resistance ULM-0.12-220 Ohm-I 220 Ohm i
R2-6 00 467 019Th Resistance ULM-01.12-4.7 kOhm-I 4.7 kOhm
R2. 0Zh0467 003TU Resistance MLT-1.1.5 kOhm-I 1.5 kOhm 1
Nue
R2-9 OZh0467 003TU Resistance MLT-1-1 kOhm-I 1 kOhm
R2-10 0Zh0467 003TU Resistance MLT-1-43 kOhm-II-B 43 kOhm
R2-12 0Z110467 003TU Resistance MLT-1-10 kOhm-II-B 10 kOhm
R2-13 OZh0467 003TU Resistance MLT-1-47 kOhm-II-B 47 kOhm
R2-14 0Zh0467 003TU Resistance MLT-1-68 kOhm-II-B 68 kOhm I
R2-15 0Zh0467 003TU Resistance MLT-1-220 Ohm-II 220 Ohm
R2-16 OZh0467 003TU Resistance MLT-1-4.3 MOhm-II-B 4.3 MOhm
R2-17 OZh0467 003TU Resistance MLT-4.3 MOhm-II-B 4.3 MOhm
'tome SECRET
-246-
50X1-HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
nreonnm
Declassified in Part- Sanitized Copy Approved forRelease2012/04/12 : CIA-RDP78-03066R000300170001-9
ow. I -FILJIVI
Nomenclature of Elements
PoST4.1.'
Design.
State National
Standard, VTU
Normal Drawing
Basic
Data
Rated
No
Notc
R2-18
OZh0467 003TU
Resistance MLT-1-4.3-II-B
4.3 MOhm
1
R2-19
0Zh0467 003TU
Resistance MLT-1-4.3-II-B
4.3 MOhm
I
R2-20
0Zh0467 003TU
Resistance MLT-1-2-k0hm-II
2 kOhm
I
R2-21
0Zh0467 003TU
Resistance PEV-10-3-k0hm-II
3 kOhm
I
R2-22
0M0467 003TU
Resistance MLT-2-1MOhm-II-B
]'MOhm
R2-23
0Z110467 003TU
Resistance MLT-2-1M0hm-II-B
1 MOhm
R2-24
0Zh0467 003TU
Resistance MLT-2-1MOhm-II-B
1 MOhm
1
R2141r
0Z110467 003TU
Resistance MLT-2-100 Ohm
100 Ohm
1
R2-28
OZ110467 003T0
Resistance MLT-1-1kOhm-II
1 kOhm
R2-29
OZ110467 003TU
Resistance MLT-0.5-100kOhm-I
100 kOhm
I
R2-31
0Zh0467 003TU
Resistance MLT2-240kOhm-II-B
240 kOhm
I
R2-32
OZh0467 003TU
Resistance MLT-05-2.7 kOhm-II
2.7 kOhm
I
R2-33
OZh0467 003TU
Resistance MLT-2-12-kOhm-II-B
12 kOhm
I
R2-34
0E110467 003TU
Resistance MLT-0.5-100 Ohm-I
100 Ohm
1
- 247 -
SECRET
50X1-HUM
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Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1-HUM
Nomenclature of Elements
Pos.
Design
Rs-35
R2-36
State National;
Standard, VTU
Normal Drawing
Name and Type
Basic
Data
Rated No. Notu
OZhO 467 003TU Resistance MLT-2-1.2MOhm-II-B 1.2 MOhm
OZhO 467 003TU Resistance MLT-1-4.3MOhm-II-B 4.3 MOhm
R2-37 OZhO 467 003TU Resistance MLT-1-4.3MOhm-II-B 4.3 MOhm
R2-38 OZhO 467 003TU Resistance MLT-1-100kOhm-II-B 100kOhm
R2-39
R2-40
OZhO 467 003TU Resistance MLT-1-8200kOhm-II-8820kOhm
OZhO 467 003TU Resistance MLT-2-240kOhm-II-B
240kOhm
1
R2-41
OZhO 467 003TU Resistance MLT-2-220 Horn-II-B
220 Ohm
R2-44
OZhO 467 003TU
Resistance MLT-1-2kOhm-II
2k Ohm
R2-45
OZhO 467 003TU Resistance MLT-0.5-3.9-kOhm-II3.9k0hm
R2-46
OZhO 467 003TU Resistance MLT-0.5-3.3-kOhm-113.3kOhm 1
R2-47
OZhO 467 003TU
Resistance MLT-0.5-220-Ohm-II 220-Ohm
R2-48
OZhO 467 003T1J
Resistance MLT-0.5-30-kOhm-II130-kOhm
1
R2-49
OZhO 467 003TU
Resistance MLT-0.5-220-Ohm-II 220-Ohm
1
R2-50
OZhO 467 003TU Resistance MLT-0.5-3.3-kOhm-113.3-kOhm
R2-51 OZhO 467 003TU
Resistance MLT0.5-100k0hm-IIB1100-kOhm 1
R2-52 OZhO 467 003TU
Resistance MLT-0.5-220kOhm-II
220 kOhm 1
R2-53 OZhO 467 003T0
Resistance MLT-0.5-14Ohm-II-B
1MOhni
-2148-
S-E-C-R-E-T
50X1-HUM
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Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1 -HUM
Nomenclature Of tLements
pos.
desig.Standard,VTU
State National
Normal Drawing
.
Name and Type
Basic Data
Rated
Note
NO
R2..5L
OZhO 467 003TU
Resistance MLT-0.5-1.5-kChm-II
1.5 kOhm
R2.51
OZhO 467 003TU
Resistance MLT-0.5-2.4-kOhm-II
2.4 kCilm
R2-56
OZhO 467 003TU
Resistance MLT-0.5-2.2-kOhm-II
2.2 kOhm
R2-57
OZhO 467 003TU
Resistance MIT-0.5-12-k0hm-II-B
12 kOhn
1
1
I--
i 1
R2-58
OZh0.467 003TU
Resistance MLT-0.5-12-kOhm-II-B
12 kOhm
R2-59
OZhO 467 003TU
Resistance MLT-0.5-100-k0hm-II-B
100 kOhm
wa.4-60
OZhO 467 003TU
Resistance MLT-0.5-100-k0hm-II-B
100 kOhm
R2 61
OZhO 467 003TU
Resistance MLT-0.5-100-kOhm-II-B
100 kOhm
R2-62
OZhO 467 003TU
Resistance MLT-0.5-15-k0hm-II-B
15 kOhn 1
R2-63
OZhO 467 003TU
Resistance MLT-0.5-15-kOhm-II-B
15 kOhm
R2-64
OZhO 467 003TU
Resistance MLT-0.5-470-k0hm-II-B
470 kOhm
1
R2-65
OZhO 467 003TU
Resistance MLT-0.5-12-kOhm-II-B
12 kOhm
1
1
R2-66
OZhO 467 003TU
Resistance MLT-0.5-39-kOhm-II-B
39 kOhn
R2-67
OZhO 467 003T1.J
Resistance MLT-0.5-100-kOhm-II-B
100 kOhm
1
R2-68
OZhO 467 003TU
, Resistance MLT-0.5-100-kOhm-II-B
100 kOhm
1
_ 249 -
SECRET
50X1 -HUM
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Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1-HUM
pos.- State National
desig. Standard, VTU,
Normal Drawing
R2-6 OZhO 467 0037U
R2-7 OZhO 467 003TU
R2-7 474 685 057
R2- OZhO 467 003TU
R2-7 OZhO 1467 003TU
R2-7 OZhO 467 003TU
R2-77 OZhO 467 003TU
R2-78 OZhO 468 004TU
C2-1 UBO 460 015 TU
0-2-2 UBO 460 002 TU
C2-3 UBO 460 002 TU
C2-4 UBO )460 002 TU
Nomenclature of Elements
Name and Type
tlasic Date
1Rated
Resistance 1416T.0.5-100-k0ktm-11 B
Resistance /ST-0.5-24-k0hm-II-B
Resistance ILZ-43-20-k0lsa-II
Resistance MLT-0.5-36-kblim-II-B
Resistance -B
Resistance I4LT-0.5220-k0iun-IT
NICOOMOlit
Resistance MLT-0.5-470-k0hm-IrB
Resistance MLT-0.5-3-k0bmi.di
Resistance MIT-0.5-560-kOhm-I
100 kOhm
2) kChm
20 kObm
36 kOhm
33 kOhm
Resistance SLI-II-2a-330-kOhm-II
Capaditor-mor-sx-lo6o
Capacitor 03-10-1000
Capacitor K03-10-1000
220 kOhm
470 kOhm 1
.4.4?114
3 kOhm 1
560 kOhm 1
330 kOhn 1
1000 pf
1000 pf
1000 pt
Capacitor KW-la-1000 1000 pt
250 -
!;1J(1414:1
kr j c a
y
50X1-HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Nomenclature of Elements
pos. State National
desig.Standard, VTU
Normal Drawing
Name and Type
50X1-HUM
as ic
ata rates No. Nott- .
C2-5 UBO 460 047TU Capacitor OK-a-N..3323 0 % -35
C24
UBO 460 00 TU
Capacitor 1DS-1a-1000
02,7
UBO 460 002TU
Capacitor EDS-la-1000
1000 pf
1000 pf 1
C2-9
UBO 460 015TU
Capacitor K0-1-14,1000
1000 pf
C2.10
UBO 1160 015TU
Capacitor K0-1-N-1000
1000 pf
UBO 460 015TU
UBO 460 OhlTU
Capacitor K0-1 -N -1000
Capacitor KTK-0-1).100 ?3.0% -35
C2.13
Oz40 452 011TU
1000 pf
100 pf
Capacitor BON-2-400-0 05-II 0.05 pf
C2-14
MO 452 011TU
Capacitor BGM-2-1400-0.01-II 0.01 Pf
C2-15
OZhO 1052 022-TU
Capacitor "MEIGP-2-40041-a1-II
C2-16
OZhO 461 oivu
2-al 1
Capacitor 130-8-2500-6-2000-II 2000 pf
C2-17
OZhO 462 011TU
Capacitor BOK -2-400-0.01 -11
0.0114
with
CV-
0-
C2-18 OZhO 462 009TU
Capacitor GT-1000-0, -II
0.5/0
C2-19
OZhO 462
022 TU
Capacitor MBGP-2-400-2.0.1-II
2-0.1
- 251 -
ACRET
toce:t r
with
C2.4"3
50X1-HUM
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Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1-HUM
Nomenclature of Elements
pos. State National
desig.Standard, VTU
Normal Drawing
C2-2L OZhO 462 022TU
C2-21 OZhO 462 011TU
C2-22 OZhO 442 011TU
Name and Type
IBasic No.
data
rated
Capacitor M130?-2-400-2-0.1-II 2-0.1
Capacitor B0M-1-400-0.05-11
Capacitor B-1-140O-0, 05-Il
,ogetip.w
with
0.05pf 1 .
0.05pf 1
C2-23 OZhO 462 011Th
C2-24 OZhO 462 001TU
Capacitor B!-1-b00-0.O5-II 0.05 t'
Capacitor Bam-1-00-0.05-11 0.05r,
C2-25 OZhO 462 002TU Capacitor KDS-la-1000-II
1
1000 pf 1
C2-26 OZhO 462 022TU
32-27 UBO 460 015TU
C2 -28"UBO 460 015TU
C2-29 OZhO 452 011Th
C2-3) UBO 460 002TU
C2-31 UBO 462 009TU
C2m18 UBO 462 009Th
Capacitor MBGP -2-400 -2 -0.25-II 2-025 tioget
ith
2-15
Capacitor K0-1-N-1000 1000 pf
Capacitor K0-10-1000
Capacitor BGM-1 -400-920-II
Capacitor 1S-10-1000-II
Capacitor M13GT-1000-0.25-11
1000 pf
920 pf
1000 pf 1
0.25f 1
Capacitor MBGT-1000-0.5-II 0.5 rf
252-
50X1 -HUM
i'7,CRET 50X1 -HUM
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Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1-HUM
'omen lature of Elewints
**..-Zi.
design
State National
Standard, VTU,
Normal Drawing
Name and Type
Basic
Data
Rated .No. ;Note
clh,
C2-34
OZhO 462 CI1TU
Capacitor B0M-2-400-0.01-I1
0.01p1
.....----,??.
C2-35
UBO 460 029TU
Capacitor KO-141-1000-II
1000,4
,......?
C2-36
0M4 600 001TU
Capacitor IDS-la-1000
1000 pf
......,
C2-37
OZh4 600 001TU
Capacitor IDS-la-1000
1000 pf
...?
02-38
OZh4 600 001TU Capacitor KDS-1a-1000
1000 pf
02-39
OZh4 600 001TU
Capacitor cs-la,lcoo
1000 pf
C2-40
UBO 460 029TU
Capacitor 10-1-N-1000-Il
1000 pf
C2-41
OZhO 462011TU
Capacitor BC24-1-00-0.01-II
0.01 rf
C2-42
UB0 460 029TU
Capacitor KD-1-N-1000-II
1000 pf
. 1
02-43
OZh4 600 001TU
Capacitor XDS-1a-1000
1000 pf
1
C2-44
OZh4 600 001TU
Capacitor KDS-la-1000
1000 pf
1
C2-45
OZh4 600 001TU
Capacitor KDS-1a-1000
1000 pf
; -
C2-46
UBO 460 041TU
! Capacitor MK-A-M-124.10% -30
:12 pf
C2-47
UBO 460 041T13 Capacitor KT1-A-14-3.9?10% -30
3.9 pf
1
C2-48
OZhO 462 011TU PAPP_Pitor BOK.1-J0-00.17tII
20.0141f
_253-
ECRET
50X1 -HUM
50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1-HUM
Nomenclature of Elements_
State National Basic Da
os. Standard, VTU, Data
esi n Normal Drawl - Name and Type Rated 1o._ote
249 UBO /460 041TU Capacitor IC175441-14.7?10% -30 147 pf 1
\MO. 440..immodiamb..-.....mm6-6.6wem Ist 6-- W.
C2-50 UBO .460 041TU
Capacitor KM-A4-4740% -30 47 Pr
C2-51 OZhO 462 011TU 1Capacitor Bart-2-400-0.01-n 0.01te
C2-52 MO 462 011Th Capacitor Bam-1-00-0.01-II 0.01 1
1
C2-53 OZhO 462 011Th Capacitor BC24-2400-0.01-II 0.011aE
C2-94 .11B0 1460 041TU Capacitor KTIC-A-M-10i10% -36
C2-55 :0ZhO /462 011Th Capacitor BO-2-400-0.01-H
C2-56 0Z110 1462 011Th 'Capacitor BGM-2-1400-0.01-II
10 pf
-????????????????????61.-
C2-57 OZhO 462 022T1J Capacitor }T-1-200-2 .0-II
C2-58 UBO 460 041TU :Capacitor KTE-A-11-27?10%-3$
0.01pf
2.05ef
C2-59 UBO 460 002TU Capacitor KDS-la-1000-II2
2-60 UBO 460 002TU Capacitor 0S-1a-1000-III
pf 1
1000 pf 1
.:6????????11.1-0.
4
C2-61 UBO 460 002TD Capacitor KDS-1a-1000-III 1000 pf
1J2-62 UBO 1460 0O2TU Capacitor KDS-1a.1000-III 1000 pf
6800 pf
02-63 UBO 460 002TU Capacitor KOS-3a-6800-III
- 254 -
r:11",RET
50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized' Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1-H UM
Nomenclature of Elements
pos. State National
des .Standard, VTU,
Normal Drawing
; Basic
; Data
Name and Type Rated No. jot.
2-64
UBO 464 005TU
Capacitor 00-0-150-II 1150 pf 1
i
Capacitor KDS-la-1000-III ,1000 pf 1 ,
1000 pi 1
C2-65
UBO 460 002TU
2-66
UBO 460 002TU Capacitor KDS-la-1000-III
C2-7q
GraCh 775.0023
OZ110 460 011TU
GUCh 777 0045P
GUCh 777 0055P
OUCh 777 0045?
,OraCh 777 0113
GYaCh 777 013S
, AR-50-2-5-1
Coil, Induction
Capacitor B1(-1400-0. 0-II
Choke Coil filament, D-2.441
Choke, 1ar-D-0.15-20p
Choke, Coil filament,D-2.4-51.
Coil, Induction, 2.5F-h?5%
Coil, Induction, 4.11rh=0.1
2.8 fda
Coil, Induction, 5 ph 5 ph
AR-1-1-2-D-0B2
Coil, Induction, 75#h
75 j.th
1
10
OUCh 777 0048P Choke D-0.1.450 Fh ?596
450 Ph
12-11
OUCh 777 004SP Choke D-0.4-51,0115%
5 ph
L2-12 GUCh 777 004SP Choke D-0.15-5.1 frh-15%
5 ph 1
-255-
50X1-H UM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
lgamenclature of Elements
50X1-HUM
p
ossi
eg.
al
State National
Standard,
Normal Drawing
'Basic
Data
Name and Type Rated No. Beim ui
12-13
GUCh 777 0014.SP
Choke D-0.15-5.1 "ht 5 Z
5.1 ph
?
L2-114
GUCh 777 000?
Choke D-0.15-5.1-044 1
5.1 f'h
?..... .,
L2-15
GUCh 777 OOLISP
Choke D-0.15-5.1 $th II
5.111h
I
?. .
12-16
GUCh 777 004$P
Choke D-0.15-5.1 Ph 1.1
5.1 rh
i
1
12-17
GUCh 777 000?
Choke D-0.15-5.10 1.5%,
5.1 rh
L2.18
GUCh 777 0035?
Choke,Filament-1.2-5?1070
5 rh
12-19
AR50-2-52.000
Choke,Filament-0.6 Ph
0.6 rh
L2-20
araCh 777 0103
Coil Induction-1.6 Ph
1.6 tit
1
12-21
GraCh 777 0090
Coil, Induct.-2.8 Ph
2.8 r.
L2-22
GUCh 777 0038?
Choke,IF-D-0.15-20 Pal
20 ph
1
_-
12-23
GraCh 775 0023111 Coil, Induct.
2.8 ish 1
_____.1.
.
....
Dr2-1
AR50-2-61-000 Choke, Charging
1
12-25
GUCh 777 004SF Choke D-0.15-39 P,10:57,
39 th 1
_ _?
Tr2-1
GiaCh 770 0010 Transformer, RF
! i
I
--i
!Tr2-2 GraCh 770 015STI Trandformarsii_
- 2% -
SECRET
50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
_ jignenclature of Elements
pos.
desigNormal
'State National
[Standard, VTU,
Drawing
Basic .
Data ,
Name and Type :Rated No, liote
Tr2-3
GYaCh 720 005SP
,
Transformer, Impulse I
fr2-4
4.
GYaCh 712 0033P
Transformer, RF
i.
Tr2-5
GraCh 720 026SP
Transformer, Impulse
1
Tr2-6
GYaCh 710 068SP
Transformer, Filament
....____
1 -
Tr2-7
GYaCh 710 0010P
Transformer, RF
1
Tr2-8
GYaCh 770 013SP
Transformer, RF
.
1
1
Tr2-9
TU-9575
Transformer
1.95/2.5r
1-1
1 '
Tr2-1O
GYaCh 714 036SP
Transformer, Anode Filament
I
C2-67
OZhO 46-10-15'TU
Capacitor K30-8-2000-B-4300-I
4300 pf
C2-68
OZhO 46 -10-15TU
Capacitor K50-8-2000-B -4300-I
4300 pf
....__- ...
C2-69
OZhO 46-10 -45TU
Capacitor KS0-8-2000 -B -4300 -I
4300 pf
1
i
C2-78
OZhO 46-10-15T
Capacitor KSO-8 -2000-B -4300 -I
4300 pf
!
1
LF2 -1AR50-2
-59 -000
Pulse Shaping Line
a Va a 1
a an ., Oh , a ... a ? ...a.
a. a. - -
-.1. tzajo-oi-uuir ueater o sc arg ng tube
LF2-1 IRN2-21-000
Thermostat
- ,257 -
nen?
50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1 -HUM
pos. State National
desig Standard, VTU,
Normal Drawing
Iiionenclature of Elements
Name and Type
Basic
Data
Rated No.
Note
1272-1 Electric Motor D-
0
oKB p/Ya 174
12-1 ChTU 01-318-56 Tube 6Zhat
12-2 ChTU 01-318-56 Tube 6ZhIB
-.???????11.
12-3 CIITU 01-105-55 Tube 6N1P
12-4 T53-301-000TU Tube 6N3,?
L2-5 TS3-341-000TU Gas Rectifier TKh-2
12-6 TS/3!41-000TU Gas Rectifier TKh-2
L2-7 ChTU-10-311-56 Thyrotron Tdr-1-35/3
124 T3-174-50S Spark Discharger R-1
12-9 VChTU06-609-51 Magnetron MI-158
12-10 TS3-341-000TU Gas Rectifier TKh-2
12-11 Ya14032-032TU Clystron K-27
1111???????????????????la
12-12 Ta10332 002T4Discharger *21
-258-
50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 26.1-0-47/12 : CIA-RDP78-03066R000300170001-9
Poe.
des.
State National .
Standard, 11Th,
Normal Drawing
Nomencla ture of Elements
Basic
Data
Name and Type Rated NO.
Note
12-13
ChTU-12-102-53 Discharger RA-50
42-15
_2-16
L2-17
-2-18
ChTU02-300-9
01317-57TU
chTu-01-103-55
ChT1J-01-103-55
Tube $G-59
Tube 6$ 7O
Tube 6Zh
Tube 6zhip
[2-19 ChTU-01-108-55 Tube 61Cap
12-20 T83-301-000TU Tube 6N3P
L2-21 ChTU-01-105-55 Tube 6N2P
F2-1 GM 540 010516
Plug-and-Socket,RF,VR-10
F2-2 GYaZ 540 018 Plug-and-Socket. Transition
F2-3 GUZ 540 008SP Plug-and-Socket, RF
GUZ 540 008SP Plug-and-Socket, RF
GUZ 540 010SP Plug-and-Socket, RF,VR-8
, GUZ 540 010SP Plug-and-Socket, RF,ATR-8 1
- 259 -
SECRET
-
50X1-HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
-
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
State National:
pos. Standard, VTU,
des. Normal Drawing
Nomenclature of Elements
Name and Type
T2-7 G"faZ 540 020 Plug-and-Socket, RF,
KT2-1 Control Point
50X1-HUM
tat; ic
jiata
rated No.
1
1
KT2- TU-211 61 Control Point
KT2- TU-111 61 Control Point
3h2-1 AR18-2-72b05 Plug, 5-Pin ,Plug
8112-2 AR18-2-78b03 Receptacle, 5-jack Receptacle
5h2-3 VW-364-006TV Plug ROCh0P17NShl
3h2-L GraZ 095 001SP Plug 11-Pins Plug
1
1
1
1
1
Sh2-5 Gra 695 001SP Receptacle, 11-Jack Receptacle
V2-1 Vr4-602-0015P-
?????????"...
Swithh
,,....mm?????????
D2-1 ChTU-014-110-57 Cry-eta]. Detector DGS61
.2.2 1(JTU-04-110-57 Crystal Detector DGS-N
-???????.0.-
1
D2-3 4hTU-014-110-57 Crystal Detector DGS-V
02-liChTU-014-110-57 Crystal Detector DGS-V
- 260 -
SECRET
1
50X1-HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
- Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1-HUM
-Awe
List of Elements
??????????ei
Note
Pos.
Desig.
State National
Standard, VTU,
Normal Drawing
rtasic
Name and Type
I
Data
Rated No.
1
3
4
OZh0-14.67-003TU
Resistor, MLT-0.5-150 Ohm-I
150 Ohm
R-14
OZh0-467-003TU
Resistor, MLT-0.5-150 Ohm-I
150 Ohm
R-3-3
OZh0-1467-0037U
Resistor, MLT-0.5-220 Ohm-I
220 Ohm
R-3-14
OZh0-467-003TU
Resistor, MLT-0.5-3.9kOhm-I
3;9kOhm
1
R-3-5
0zh0467 -093TU
Resistor, MIIT..0 ? 5'3 ? 3k013M'd
3 ? 3kOhni
1
R-3-6
OZh0-467-003TU
Resistor, MLT-0.5-220 Ohm-I
220 Ohm
1
......???????????4
R-3-7
OZh0-467-003TU
Resistor, MLT-0.5-5.1kOhm-I
5.1kOhm
1
R-3-8
0ZhO-467-003W
Resistor, MLT-0.5-3.9kOhm-I
3 .9k0bm
1
R-3-9
OZh0-1167-003TU
Resistor, MLT-0.5-19 kOhm-I
10 kCalm
1
R-3-10
OZh0-467-003TU
Resistor, MLT-0.5-220 Ohm-I
220 ObmI
1
R-3-12
On0-467-003TU
Resistor, MLT-0.5-5.1k0hm-I
5.1k
R-3-13
OZh0-467-003TU
Resistori MLT-O. 5-10 kOhm-I
10 k
R-3-14
OZh0467-003TU
Resistor, MLT -0.5-3.9kOhm -I
Ok0
R-3-15
OZh0-467-003TU
Resistor, MLT -0.5-220 Ohm-I
220
_ 263. -
50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1 -HUM
List of Elements
PCG.
Desig.
State National
Standard, VTU,
Normal Drawing
Name and Type
Basic
Data
Rated No. : Not
R-3-17 i OZh0-467-003TU
Am.=
Resistor, MT-0.5-3.9k0hm-I 3.9kOhm 1
R-3-18 OZh0-467-003TU
R-3-19 OZh0-467-003TU
R-3-20 0Zh0-467-003TU
02,h0-1467-003TU
R-3-23 OZh0-467-003TU
R-3-25 OZh0-1467-oo3TU
R-3-26
OZh0-467-003TU
R73.27
OZh0-467-003TU
R.3-28
On0-1467-003TU
R-3-29
OZh0-1467-003TU
R-3-30
OZh0-467-003TU
R-3.31
02h0-14.67-003TU
1-3-31
02h0-14.67-003TU
R-3-34
OZh0-467-003T'U
Resistor, MT-0.5-5.1k0hm-I 5.1kOhm 1
Resistor, MT-0.5-220 Ohm-I 220 Oki 1
Resistor, MIT-0.5-5.1k0hm-I 5.1k0ki 1
Resistor, MIT-0.5-12kOhm-I = 12 kOhm 1
.Resistor, M1T-1-911 kOhm-I 9.1kOhn 1
Resistor, 3.3kOhi 1
Resistor, MT-0.5-22k0hm-I
4-
!Resistor, MT-0.5-680 Ohm-I
Resistor, MT-1-1.6 Ohm-I
!BAsistor, MT-0.5-430kOhm-I
!Resistor, MLT-2-220 Ohm-I 220 Ohm :1
22 kali
1
680 Ohm
1
1.6 Ohm
1
430kOhm
1
Resistor, MT-0.5-680 Ohm-I 680 Ohm 1
'l-1-
Resistor, MT-0.5-220 Ohm-I 220 Ohm 1
!Resistor, Krz-1-2a Ohm-II 2MOhm
- 262 -
ACRel
50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9 JM
Nee
List of Elements
Pos.
Desig.
'State National
Standard, VTU,
Normal Drawing
Name and Type
R-3-35
02h0-1467-003TU
Resistor, MIT -1 -10kOhm-II
3-36
OZh0-1167-003TU
Resistor, MLT-1-62kOhm-I
R-3-37
OZh0-467-003TU
tesistor, MIT-1-33kOhm-II
3-38
OZh0-1467-003TU
t.esistor, KLT-1-15 NOhrn-II
3-39
02h0-467-003TU
Resistor, MLT-1-5.1MOhm-11
3-40
OZh0-467-003TU
IResistor, MLT-1-12140hm-II
R-3-41
MO467-003M
!Resistor., MLT -1 -916kOhm -II
-42
02h0-467-003TU
Resistor, NIS -1 -20kOhn-II
3-43
02h0-467-003TU
Resistor, MLT-1-100kOhm-II
-44
OZh0-1467-003TU
Resistor, MI,T -1 -62kOhm-II
-45
02h0-1467-003TU
Resistor, MLT -11-6.8kOhm -II
-46
0Zh0467-003TU
Resistor, MLT-1-430 Ohm-II
R-3-47
OZh0-467-003TU
Resistor,}.T-1-510kOkun-II
R-3-48
MO-467-0031T 'Resistor,
MLT-1-330kOhm-II
R-3-49
02h0-467-003TU
Resistor, MLT-1-200kOhm-II
-263-
Basic 7
Data
Rated Note CI's.
10kOhm 1
62kOhm 1
33kOhm
NOhm
5amoton
1
,12MOhm
910kOhm 1
20kOhm
100k0bm
62kOhm
6. 8kOhin
1430 Ohm I
510k0bm 1
330k0hm ! 1
200kOhm
1
50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
i-riuM
OW\
Pos.
Desig.
State National
Standard, VTU,
Normal Drawing
R-3-50
OZh0-467-003TU
OZh0-467-003TU
R-3-52
OZh0-467-003TU
R-3-51
MO-468-0031U
R-3-54
OZh0467-003TU
R-3-55
OZh0-467.003TU
R-3-56
NIP4-675-001AN
R-3-57
vP4-675-ooto
R-3-58 VP4-675 -wow
List of Elements
Name and Type
Basic
Data
Rated No. Note, 00,.
Resistor, ELT-1-66kOhm-I 68kOhm 1
Resistor, MLT -1-680kOhm 680kOhm 1
Resistor, ELT-1-330kCiam-II 330kOhm 1
Resistor, SR-14a-1.2A-13 1.2kOhm 1
Resistor, MLT-0.5-1.5kOhm-I 1.5kOhm I
Resistor, MIT-1-470-ketra-II
sistor, NT.0.5-8.2 kOhmtl% 8.2k0
.1-
esistor, PT.0.5-3.3 kOhmtl% 3.3k0
sistor, PT.0.5-2 kOhmil% 2kOhm
R.3-59 I VP4-675-004SN *sistor, k0hm=1% IkOhm 1
?R-3-60040Kh4-685-018SP Resistor, 120kOhm
k.3-65 ;NUM-685-018SW fiesistor, PP4.II-10-kOhm,I
10kOhm
R-3-66 VP14-675-004SP
Resistor, PT-0.5-6.8kOhm=196
R-3-67 OZ1,Ou46/-003TU
Resistor, ELT -1 -15 kOhm-I
mow
OZ110-467-003TU Resistor, ELT-14.4 kOhn-II
6.6kOhm
15 kOhm 1
.4 kOhm
- 264 -
"ITTrq
50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1-HUM
List of Elements
State National
Pos. Standard, VTU,
Desig. Normal Drawing
Name and Type
Basic
Data
Rated No. Note Ch.
R-346 OZh0-467-003TU Resistor, MLT-2-4.3 km-1 4.3 kOhm 1
1-3-70 0Zh0-467-003TU
Resistor, MLT-1-560 kOhm-I
560 kOhm 1
R-3-72 Gra4.675-009
Resistor,PT-I-P682 k0hmt0.1682kOhm
R-3-73 Gra4-675-009
Resistor, PT-IM-82 k0hm=0.5t 82 kOhm
1
R.3-74 0M487-003M
Resistor, MLT-T-680 kOhm-II
680 kOhm
1
1
1
R-3-75 VP4-675-004SP
MLT--1-30 k0hn419s
30 kOhm
R-3-76 OM467-0032U
MLT-I-10 kOhm-II
10 kChm
R-3-77 It
MLT-1-24 kOhm-II
24 kOhm
1
II
R-3-78
MLT -I-10-kOhm -II
10 kOhm
tl
R-3-79
kOhm-II
2.14 kOhm
1
R-1-80
IT
MLT-I-31? kOhm -II
3q kOhm
1
I
R-3-81 It
MLT-I-100
100 kOhm
R-3-82 It
MLT-I-100 kOhm-II
100 kOhm
1
R-3-83 14
MLT-I-68 kOhm-II
68 kCbm
1
R-3-85 It
MLT-I-100 kOhm-II
100 kOhm
1
_ 265 -
1!,,Y71,171
50X1-HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1 -HUM
List of Elements
POS.
Desig,
saw'
State National
Standard, VTU,
Normal !Hy:ming__
Name and Tipe
Basic
Data
Rated No. Ne,e CL
R-3-86
0Zh0-467-003TU Resistor, MLT-I-100 kOhm-II 100 kOhm 1
R-3-87
MLT-I-68 kOhm-II
68 kOhm 1
R-3-88
MLT-0.5-1.2 kOhm-II
1.2k0hm 1
R-3-89
MLT-1-5.1 kOhm-II
5.1 kOhm 1
R-3-90
MLT-I-430 kOhm-II
430 kOhm 1
R-3-91
?
MLT-2-20 kOhm-II
20 kOhm 1
R-3-92
kOhm-II
3.0 kOhm 1
R-3-93
tt
MLT-I-510 kOhm-II
510 kOhm 1
R-3-94
It
kOhm-II
3 kOhm 1
R-3-95
It
MLT-I-2.0 kOhm-II
2 kOhm 1
R-3-97
MLT-2-100 kOhm-II
100 kOhm 1
R-3-98
It
?
MLT-I-220 kOhm-II
220 kOhm 1
R-3-99
It
MLT-I-510 kOhm-II
510 kOhm 1
R-3-100
It
MLT-2-22 kOhm-II
22 kOhm 1
R-1-101
ft
MLT-I-100 kOhm-II
100 kOhm 1
-266-
.CRT
50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9 j
Avow
Pos. State National
Pos. Standard, VTU,
Desig. Normal Drawing
List of Elements
basic
Name and Type Data
Rated No. Note C.
R-3-102 OZh0-467-001TU Resistor, MLT-I-200 kOhm-II 200 kOhm 1
R-1-103
MLT-I-100 kOhm-II 100 kOhm 1
R-3-104
/I
? MLT-I-13tk0hm-II 130kOhm 1
R-3-105
It
MLT-I-1.0 kOhm-II 1.0 kOhm 1
R-3-106
tt
? MLT-I-820 kOhm-II 820 kOhm 1
R-3-107
It
Il MLT-I-68 kOhm-II 68 kOhm 1
R.3-108
it
It
MLT-I-100 kOhm-II 100 kOlus 1
Ri.3-109
Is.
? MLT.I-39 kOhm-II 39 kOhm 1
R-3-110
MLT-I-510 kOhm-II 510 kOhm
R-1-111
MLT-0.5-12 kOhm-II 12 kOhm 1
R-3-112
ft,
MLT-I-510 kOhm-II 510 kOhm 1
R-3-113 NGICh4?6685-018SP
FPI-II-20 kOhm-II 20 kOhm 1
R-3-114 OZh0467-003TU
11
MLT-I-1.1 kOhm-I 1.1 kOhm 1
MLT-I-300 kOhm-I 300 kOhm I
R-3-116
ft
MLT-I-2.0 kOhm-II 2.0 kOhm 1
- 267 -
nVCRET
50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
SECRET
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1-HUM
List of Elements
Pos,
Desig.
State National
Standard, VTU,
Normal Drawing
Name and Type
Basic
Data
Rated No Note (4
R-3-118 OZh0-467-003TU
Resistor, MLT-I-1.0 MOhm-II
1.0 MOhm 1
R.3-119
It
Resistor, MLT-I-150 kOhm-I
150 kOhm 1
R-3-123
It
MLT-I-1.0 MOhm.II
1.0 MOhm 1
R-3-124
It
MLT-I.300 kOhm -I
300 kOhm 1
R-3-125
ft
27 kOhm I
R-3-1a6
It
It
MLT-I-560 kOhm-I
560 kOhm 1
R-3-127
It
It
MLT-I-200 kOhm-I
200 kOhm 1
R-3-128
Ii
MLT-I-200 kOhm-I
200 kOhm 1
R-3-129
II
U
MLT-I-6.8 kOhm-I
6.8 km 1
R-3-131
If
II
MLT-I-100
100 Ohm 1
R-3-133
Is
MLT-0.5.47 kOhm-II
47 kOhm 1
R-3-134
It
MLT.I-51 kOhm-II
51 kOhm 1
R-3-137
It
It
MLT-I-82 kOhm-II
82 kOhm 1
R-3-138
Is
kOhm-II
6.8 kOhm 1
- 268 -
311k,21.1!
50X1-HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2-012/04/12 : CIA-RDP78-03066R000300170001-9
Qum -HUM
List of Elements
wow?
Pos.
Desig.
State National
Standard, VTU,
Normal Drawing Type
Data
Rated
No. Note 1i
R-3-139 0Zh0-467-003TU Resistor, MLT-I-150 Ohm-II
150 Ohm
1
R-3-140
tt
MLT-I-68 kOhm-II
68 kOhm
R-3-1/43.
MLT-I-3.3 kOhm-II
3.3 kOhm
1
R-3-1.42
ft MLT-I-510 kOhm-II
510 kOhm
I
C3-5
TU-I-0Zh0-460-001 Capacitor KDO.1a-1000
WOO pf
O3-1
KO].-N-1000-II
03.2
Tij.?I.0ZW-4460-001 KDS-la-1000
C3-3
tt ft
c3-4
It; It II
It
C3-7
03-6
TU-I-OZ110-460-001
R0-1a-1000-H
1
C3-8
117
It
KDB.1a-1000
It
C3-9
It
II
It
II
C3-10
ft
II
KI-la-.1O00
It
1
C3-11
ft
ft
It
- 269 -
50X1 -HUM
:!177vrT 50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9 11V1
List of Elements
Aloe
Pos.
Desig,
State National
Standard, VTU,
Normal Drawing
Name and Type
Basic
Data
Rated
No
Icte
1
2
3
4
5
,k
f
C3-12
Tu-I-0Zh0-460-001
Capacitor, KDS-la-1000
1000 pf
1
C3-13
UBO.462-017TU
It
WI-T-1-680-V
680 pf
I
C3-14
TU-I-OZh0-460-00
ft
KDS-la-1000
1000 pf
C3-15
II
ft
C3-16
It
It
ka.,Mkkall/ok?
C3-17
UBO-462-017TU
C3-18
TU-I-OZh0-460-001
It
03-19
TU-I-OZh0-460-001
ft
ft
II
C3-20
C3-21
ft
ft
1
C3-22
TU-I-OZh0-460-001
II
ft
03-23
02110-460-014TU
ft
KTK-12tt-5 pf-I
5 pf
I
Select.
C3-24
TU-I-OZh0-460-001
K0-lk-22 pf -II
22 pf
C3-25
TU-I-OZh0-460-001
KDS-la-1000
1000 pf
C3-27
MO-460-014V
It
KTK-lm-27 pf
27 pf
1
71114101,r-
SECRET
50X1-HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
ANY
List of
lements
Pos. State National
Pos. Standard, VTU,
Destg, Normal Drawing
Name and Type
C3-28 0Zh0-462-011TU Capacitor,B414..2-400-0.01 mf
C3+29 H
B(01-1-400-0.01- II
C3-30
ft
C3-31 TII-I-02h0-460-001 Kh0-1-I-1000-II
C3-32 MO-462-0111T
BGM-2-400-0.01-11
50X1-HUM
Basic
Data
Rated
0.01,f
No. Note C.
1
O.01,
3
1000 pf
1
0.01 pf
1
C3-33 02h0-462-0221113
It
C3-34 MO-462-011n
4010?1?1101.11a
MBGP.02-200-2g45-II 0.5 pf 1 together
with_Qt:
? 411-2.400.0.0147 0.01 pf 1
C3-35
It
It
C3-36
It
ft
C3-37 02ho-462-022TU
ft KBGP-2-200-2x0.5-ri 0.5 or 2. top- the/
C3-38 02h0-462-011TU
It
BON-2-400-0,01-11 0.01 pi' 1
C3-39 0210-462-022TU ? MOCIP-...2-400..2 0.1-II 0.1imf I together
C3-f4
C3-40 OZh0-462-011TU ? Balf-2-400-0.01mf 0.01pf 1
C3-41
ft
? BG14-2-400-0.05-11 0.05,t 1
C3-42
ft
ft
-271 -
50X1-HUM
npdassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
/4 17CLVil cn NI 4 LJ I mi
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9 '
State National
Pos. Standard, VTU,
Besig. Normal Drawing
List of Elements
Name and Type
Basic
Data
Rated No. Note ...
03-43 OZhO -462 -011TU Capacitor, 3OM4-400 -0.05 -II 0.05 mf
C345
ft
ft
BGH-2 -400 -0.01-II 0.01 mf
ft
ft
c3.46
If
ft
C3.47
OZh0-460-014TU
KTK-2a -L-330 -II 330 pf
....?:????/??4
1
C3-49
ft
KTK-3m-150 -I 150 mf
1
C3-50
MO -462 -022TU
1MOGP-2-400-ga1 0.1 mf
C3-51
UP0-464-005TU
0-2-500480-Ts-I 68- pf
-11
C3-52
OZh0-462-022TU
MOP-2-400-2 0.1,11 0.1 mf
1 togethel
wit7pC3.1,!
0-53
UP0-464-005TU
K3-1-500-0-100-11 100 pf
C3-54
OZhO -462 -011TU
WM.-2-400-0.01-U 0.01 mf
C3-55
ft
ft
B0M-2-400-1500-II 1500 pf
1
C3-6
ft
a
BM-2.400-0.01-H 0.01 mf
C3-57
UP0-464-005TU
ft
KS-1-500-0-200-I 200 pf
1
03-58
UB0-460-016TU
KTN -1-1111.100 -II 100 pf
-272-
50X1-HUM
50X1-HUM
--. SECRET
nprlacsified in Part- Sanitized Copy Approved forRelease2012/04/12 : CIA-RDP78-03066R000300170001-9
511X1 -HIIIVI
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
List of Elements
Pos.
Des ig
State National
Standard, VTU,
Normal Drawing
B3 zjc
Data
Name and Type Rated
No. late
C3-59
OZh0-462-022TU
Capacitor, MBGP-2-400-2 0.1-II 0.1 ?It'
1 to*'
C3-60
4.1.???'
0Zh0-462-011TU
II
BM-2-400-3300-n 3300 pe
1
C3-61
ft
DOM-2-400-0.01-II 0.01 mf
1
C3-62
UB0-460-016TU
KTN-1-D-100-II 0.01 mf
3.
C3-63
OZh0-462-011TU
ft
130M-2.400-0.01-II 0.01 mf
1
C3-64
0Zh0-462-0022TU
MBGP-2-400-2 0.1 mf 0.1 mf
1
C3-65
Any'
02h0-462-011TU
BGM-2-400-3.500.II 3.500 pf
3.
C3-66
B0M-2-400-0.01-II 0.01 alf
3
C3-67
02h0-462-022TU
MEGP-2-200-2-II 2 mf
1
C3-68
OZh0-460-0.35TU
KTK-1-L-100-II 100 pf
C3-69
OZh0-462-011TU
130M-2-400-0.01-U 0.01 mf
1
03-70
UP0-464-005TU
KS-1-500-200-II 200 pf
1
1 iCgtIt?IT
tth
03-71
0Zh0-462-022TU
MBGP-2-400-2X0.1-II 0.1 mf
C3-72
IIP0-464-005TU
KS-2-500-P-680-N-I 680 pf
1
03-73
02h0-462-022T13
HGP-2-200-2 0.5-II 0.5 mf
1
. 273 - 50X1-HUM
SEMI
imfin,r4 in Davi - Saniti7ed CoDv Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
SECRET
50X1-HUM
List of Elements
Pos,
Desig
State National
Standard, VTU,
Normal evawing
Basic
Data
No, Nel
C3-74
OZh0-462-022TU
Capacitor, MBGP-2-200-2 0.5-11
0.5)pt 1
0-75
0M0-462-011TII
BOM-2-400-0. 05 -II
0.05 rf 1
C3-76
ft
et
C3-77
UP0-464-0o5TU
KS-1-500 -0-100 -II
100 pf 1
C3-83
MO-462-022W
ft
MBGP-2-200-1-II
I pf 1
C3-85
02h0-462-011TU
II
BGN-2-400-0. 05-11
O. 05 /if 1
C3-86
ft
ft
0.05ipf 1
C3-8?
02h0-462-022TU
MBGP-2-200-2A0.05-II 0.051af 1
C3-88
It
It It
togetier
uTith 7f3-Ft"
L-3-1
AR50-2-52-000
Filament Choke 0.6fin
L-3-2
tt
II
1
1-3-3
IT
It 2
1-3-4
It
1
L-3-5
It
It
1
L-3-6
It
It
1
27), -
.50X1-HUM
50X1
SFICPET
-HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1-HUM
List of Elements
State National Basic
Pos. Standard, VTU, Data
Desig. Normal Drawing aiNt2ALILTEce Rated No.Note
? ? _
L-3-7 GA-777-0035P Filament, H-F-D01520 mh 20 Mh 1
1,-3-8 n n n n 1
1?.3-9 il n n
" 1
1,3-10 n n n n 1
13-1 Ci1TJ-0110-355 Radio Tube 6Zh1P 1
L3-2 n n n
L3...3 CliTUO..110.455 " 6Zh2P "
13-4 II n
n
L3-5 CATuo-110-35.5 n lZh1P II
13-6 cpuo-lio -355 n 6Zh2P It
L3-7 Ts3-301-000TU " 6Zh3P il
13-8 Ts3-302.-000TU
L3-9 ChTM-LA.-55
62h2P
L3-10
Ts3-301-000tu-I
6Zh3P
13-11 arum-105-55 map
- 275 -
STICRET
to
50X1-HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Qum -1-1U IV1
List of Elenents
State National Basic
Pos. Standard, VTU, Data
Desie. Normal Drawing_ Name and Type Rated No, )ote
L3-12 CTU-o11_855 Radio Tubs 6Zh2P
L3-13 TS3-301-000TU-1
ft
L3-14 aiTU0110455
ft
6Zh2P
L3-15 CP110118855
6Zh2P
L3-16 TS3-301-000TU-1
? 6Zh3P
L3-17 C3ITU0144055 ? 6Zh5T
11
13-18 " li n
n 1
L3-20 " n n "
13-21 " n n n
13-22 " n n
13-23 COU0110455 n 6Zh2P ft
13-25 11 M 6Zh2P II
M
L3-19 T53-301-000TU-1
6Zh3P
L3-26 CpTU0131856
L3-27 ChTU0131556
ft
ft
62h1P
6D6A
-vow -276 -
50X1-HUM
SECTET _ 50X1-HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9 I
List of Elements
Pos.
Desig.
State National
Standard, VTD,
Normal Drawing
Basic
Data
and Tyoe Rated
No Not h
L3-28
Tr-3-1
Tr-3-2
Tr-3-2
Tr-34
Tr-3-5
Tr-3-6
Tr-3-7
2-3-1
Z-3-2.
Z-3-5
L33-1
Sh3-1
Sh3-2
Sh3-3
R3-1
R3-2
R3-3
R3-4
R3-5
ChTD0131556
Gra4770013SP
ft
GYa4-710-0255P
GYa4-720-006SP
AR50-2-54-000
01a2-066-0125P
AR50-032-012SP
VN0364-0064TU
II
1RM-3-2 sb02
_Name
Radio Tube 6D6A
Transforrer, H.F.
tl
It
It
Fila me nt Transf or mer
Pulse Transforrrer
Filtering Cell
ft
ft
Line of Delay 0.4 rec.
Intra-cell d isc ?meet or
Plug R48PK2EN1
Socket R32P1(283N1
Relay RMCIO RS/4-523419D1 RS04520P2TU
tt,
ft
Coaxial Cable Socket
1
fi
II
ft
"
11
ft
Vt
ft
tt
ft
_ 277 -
. RFA
50X1 -HUM
50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
prp
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1-HUM
List of ilemants
Pos.
DesiR,
State National
Standard, VTU,
Normal Dtawing,
Basic
Data
aixi Type No.
Note
1
2
3 4
Resistor, PEV-10-10 k0hm210% 10 kOhm
KT-2-39 kOhm-P-M. 39 kOhm
MIT-1-39 kOhm-P-V 39 'Ohm
M1T-1-390 kOhm,P-V 390 kOhm
1!LT-1-390 kOhm-P-V 390 kOhm
1
1
1
1
114-1
R 4-3
R 4-4
R 4-5
OZh0-467-011TU
MO -467 -003TU
OZh0-467-003TU
MO -467 -003TU
OZ110 -467 -003TU
R 4-6
BP4-675 -001SP
FT-1-91 kOhmtlOw 91
kOhm
1
R 4-7
BM -675-002SP
FT-1-68 kOhmtl% lw 68 kOhm
1
R 4-8
NRRh4 -685 -018SP
PPZ-11-10 k0hmt1011 10 kOhm
1
R4-9
BP4-675-001SP
PT-1-56 kOhmtl% lw
56 kOhm
1
kit 4-10
OZhO -467 -003TU
MLT-510 kOhm-P-B
510 kOhm
1
R 4-11
-467-003TU
M1T-1-39 kOhm-P-B
39 kOhm
1
R 4-12
OZh0-467-003TU
M1T-1-390 kOhm-P-B
390 kOhm
1
R 4-13
BP4 -675 -001SP
PT-1-100 kOhmtl% lw
100 kOhm
1
R 4-14
BP4-675-001Sp
PT-1-68 kOhmAl% lw
68 kOhm
1
R 4-15
NO4-685 -018SP
PP3-11-10 k0hmt10%
10 kOhm
1
4 4-16
BP4 -675 -001SP
PT-1-82 kOhm*1% lw
82 kOhm
1
R 4-17
OZh0-467-011TU
PEV-10-10 k0hmk10%
10 kOhm
1
R 4-18
OZhO -467 -003TU
mu-1-39 kOhm-P-B
39 kOhm
1
_278-
..SECPET
50X1-HUM
50X1-HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1 -HUM
NNW(
List of Elements
State National
Pos. Standard, VTU,
EIPSig. Normal Drawing
1 2
Name and Type
3
Basic
Data
Rated No. Note
if 5 g
R 4-19 OZh0-467-003TU Resistor, MIT-1-390 kOhm=V-Ta 390 kOhm 1
a 4-20 0Zh0-675 -001SP
ft 4-21 NG4 -685 -018SP
R. 442 BP4 -675 -001SP
3 4-23 OZhO -467 -003TU
R 4-24 OZhO -467 -003TU
R 445 OZhO -467 -003TU
4-26 OZh0-467-003TU
R. 4..27 OZh0-467-003TU
R 4-28 BP4-675-001SP
R 4-29 BP4-675-00ISP
R 4-30 BP4-675-018SP
R 4-31 BP4-675-001SP
R 4-32 OZh0-467-003TU
R. 4-33 OZh0-467-003TU
R. 4-34 0110-467-003TU
R 4-35
it 4-36
It
PT-1-130 kOhm;1% lw
GW3..11-10 k0hm7.1% lw
PT-1-91 kOhm71% lw
14IT-2-39 kOhm-P-B
It It
MIT-1-39 kOhm-PB
130 kOhm 1
10 kOhm 1
91 kOhm 1
39 kOhm
39 kOhm 1
39 kehm 1
MIT-1-390 kOhm-P-B 390 kOhm 1
390 kOhm 1
PT-1-30 k0hm;1% lw 30 kOhm 1
PT-1-75 k0hm;1% lw 75 kOhm 1
PP3-11-10 kOhm=1% 10 kOhn 1
PT-1-35 k0hm7.1% lw 35 kOhm 1
MIT-2-3.3 kOhm-I-B 3.3 kOhm 1
MIT-1-510 kOhm-P-B 510 kOhm 1
kOhm,P-B 100 kOhm 1
MIT-1-910 kOhm-P-B 910 kOhm 1
14LT-2-39 kOhm-P-B 39 kOhm 1
_279-
50X1-HUM
50X1-HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
qTrirrprm
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R0003001700 -
State National Basic
Pos. Standard, VTU, Data
Eesig. Normal Drawing Name and Type Rated No Note
1 2 3 -4- 5 --r--
C4-1
04-2
C4-3
CLP-h,
6'4-5
C4-6
C4-7
C4-8
C4-9
Noe C4-10
C4-11
C4-12
04-13
Nor=
OZh0-462-02270 Capacitor,
II tt
II It
H TI
It It
II H
II II
OZh0-462-011TU
OZh0-462-022TU
OZh0-462-011TU
MBTP-2-600-2-II 2 pf
MBOP-2-400-0.25-II 0.25 ffif
14BCP-2-400-1(50)-II 1 ft
148GP-2-400-111.25-II 1 pf
M3CIP-2-400-1-(50)-II 3pf 1
2 pf 1
IMP-2-400-0.25-11 0.25 pf 3.
MP-2-400-1(50)-11 1 par 1
2 re 1
ME3GP-2-400-0.25-II 0.25 fir 1
3aN-2-400-0 .01-II 0.01/e 1
1413TP-2-200-1-II 1 pf
BTN-2-400-0.01-II 0.01 pf 1
PR4-1 State National Puse PK-30-2a
Standard 5010-53
PR4-2
PR4-3
PR4-4
PR4-5 II
" PK-30-0.15a
It II
- 280 -
rr.
50X1 -HUM
50X1 -HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
50X1-HUM
vire
List of Elements
Pos .
Desig.
State National
Standard, VTII,
Normal Drawing
Ba sic
Data
Name and TypeRa.ted
_
_3_ 4
Tube ahlP
Tube 670P
ho 121 !,e C
6 1
1
1
2
14-1
14-2
ChTU-01-107-55
ChTU-01-106-35
14-3
ChM-C1-107-55
Tube 6Z1AP
14-4
ChTU-01-107-55
Tube 6Zh6P
14-5
GhTU-01-106-55
Tube 6Zh6P
14-6
ChTU-01-107-55
Tube 6Zh6P
L4-7
14-8
14-9
ChTU-01-10655
Tube aba
,411,
L4-10
ChTU-01-701-54
Tube 3333
1
1)4. -1
LO-354-2006TU
Plug R32P1C93Sh2
04 -1
TR3215-108VrTII
Germanium Diode D7-Zh
Nor
D4 -2
D4-3
D4 -4
011. -5
D4-6
D4 -7
D4 -8
D4 -9
II
11
ii
II
11
11,
II
II
II
-281 -
50X1-HUM
SWRFIT 50X1-HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9
ID151,11241.
.1110me
'lope
N..=
List of Elements
State National
Pos. Standard, VT13,
Desig. Normal Drawing
1 2
50X1-HUM
Basic
Data
Name and T Rated No. Ncte Ch
3 4
1)4-10 Tr3215-108VrTU Germanium Diode D7-2h
D4-11
1D4-12
D4-13
D4-14
D4-15
D4-16
D4-17
D4-18
D4-19
D4-20
D4-21
D4-22
134-23
D4-24
D4-25
D4-26
D4-27
D4-28
D4-29
D4-30
D4-31
D4-32
D4-33
D4-34
D4-35
E4 -36
TR4-1 0347140160SP
TR4-2 G34714000SP
Tr ans f or mer
- 282 -
1
50X1-HUM
50X1-HUM
Declassified in Part - Sanitized Copy Approved for Release 2012/04/12 : CIA-RDP78-03066R000300170001-9