CONTRACT AF33(657)13264 WESTINGHOUSE REFERENCE AAD-51244

• Document Type: CREST
• Collection: General CIA Records
• Document Number (FOIA) /ESDN (CREST): CIA-RDP67B00657R000200260001-7
• Release Decision: RIFPUB
• Original Classification: K
• Document Page Count: 117
• Document Creation Date: December 9, 2016
• Document Release Date: January 27, 2001
• Sequence Number: 1
• Publication Date: September 18, 1964
• Content Type: LETTER

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Westinghouse Electric Corporation
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MAW ATLV SYSTEM
Progress Report 113.
For Period
4 through 30 Au
lF 33(657)4326k
15 September 1964
Aerospace DivisloD
Baltimore, Maryland
fig00020i 260014F7i-j/
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Pages i through viii
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TABLE OF CONTENTS
Parugraph Page
1. Introduction and Surcero.ry
J.1 Introduction 1.
1.2 Establishment of Taska
1.3 Major Events
1.4 Contract Costa
Project Tusks .
L.5.1 Anticipatory Costa
Administrstion
J..5.3 Project Syatem
0
1.6 Systems Analysis
1.6.1 Frequency Choice
1.1.2 Target Characteristics 10
1.6.3 Antenna Coverage12
1.6,3.1 Gain Pattern Lnvesti&ation
1.6.3.2 Pointing Angle and Peumwldth Pointing Investigation
1.6.3.3 Sumwary
14
16
L-6-4
Intehretion Time
16
1.6.5
Filter Bank Parameters
if
1.6.6
FRP and Duty Cycle
22
1.6.7
sigma/noise
22
1.6.0
System Pischunization
24
2..6.9
Miscellaneous Analyses
26
:..6.10 Clutter Spectrum Considerations
Table Parameters
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OF CONI'ENTS(continued)
Paragraph
1.7 System Configuration
1.7.1 Anteraxl
1. .7.2 Radar Electronics
i.!.3 Cooling Systefl
L.6 Clutter Fli&t Test ?roran
1.0.1 Purpose
1,3.General Description
1.6.3 Equipment
.6.4 Procedure
2. Active Subsystem lifaChaniZation and Integration
Mechanization am% Sequence of 4eration
2.1./ Present System Mechanization
Li .1.2 Frequency Diversity a,nd Jam Avoidance
Sequence of Opem.tion
.2 Transmitter and RF Circuits
?.2.1 Crystal Oscillator Stability
.2.2.2 Solid State Power Amplifier
;.2.3 Final RE Amplifier
,2.2.3.1 /lured Line Deformation
2.2.4 Duplexer
2.2..5 High Power Limiter
High Yolta, Power Supplies
.3 Receiver
.3.l Preselector
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TABLE OF C0NT49T3
Paragraph
2.3.1.1 Cross Modulation
2.3.1.2 Intermodulation
2.3.1.3 Noise Figure
2.3.2 Second IF Corwerter
2.3.3 in IF Amplifier and Converter
Alta Processor
2.4.-1 System Operation Sequencing
.-4.1.1 Data Processor Functional Operations
4.4.1.1.1 Timing Signals
2..4.1.1.2 Selection of Trwmaitter Frequency
2.4.1.1.3 Processing of Threshold Detection
Alarm
..!.4.1.1.5 Velocity Multiplier Amplifier Control (VMAC)
'.4.2 Mechanization
Page
(3
63
63
83
35
2.4.2.1 Circuits
f.?X.)
2 .4 .2.2 Packaging
90
2.4.3 Progress to rate
90
Clutter Tracker and Video Circuits
92
2.5.1 Clutter Tracker Mechanization
92
Clutter Tracher-Navipoitor Interface
92
5.3 Velocity Truck VCX0
93
d.5,4 Velocity Multiplier
94
Scan VCX0
94
2.5.6 Fixed Ocillator
94
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TABLE OF CONTENTS (continued)
Paragraph
2.5.( Mixers
2.5. Clutter Spectrum
2.5.9 Dating Circuits
2.6 Low Voltage Power Supplies and Special Test Equipment
Low Voltage Power Supplies
2.0.1.1 I1i Changes since Proposal
Description and Characteristics
:6.1.3 Present Status of Low Voltage Power Supplies
2.6.2 Special Test Equipment
2.7 Filter Bank and Interrogator
27.1 Cbannelization of tbe Doppler Spectrum
2.7.2 Envelope Detection and Integration
1.7.3 Commutation or Interrogation
2.0 Active Subsystem Plans for Next Reporana Period
3. Antenna Subsystem
3.1 Analysis and Mbdel Study
3.1.1 Analysis
3-1.2 Model Study Traveling Wavle Antenna
3.1.3 Plans for Next Reporting Period, Analysis and *xtel
3.2 Developilent of Elements and Dover Dividers
3.2.1 Radiating Elements
3.2,2 Power Dividers
3.2.3 Plans for Next Reporting Period, Elements and Power
3.3 brjcation and Test of Deliverable Antenna System
96
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udy 107
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10:5
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Figure
1.-.1 Required and Expected Gain Patterns
1-2 Number or Whole Looks for "Wer-t" Target
1-3 Acceptance Acceleration Band
1-4 Required Two Way Antenna Gain (ib)
c( vs Frequency Over water
146 Clutter Flight Test System Block Diagram
1-1 Systea Configuration For Calibration
2-1 Radar Black Diagram (Obsolete)
2-2 Radar Block Diagram (Current)
Left-Right Amplitude Comparator
2-4 Sequence or Operations in a Jammed Enviro (No E
2-5 Sequence or Operations for Or flit or Two Hits
2-6 Sequence or Operations Timing Diagram
2-7 Tranemitter Baock Diagram
2-0 Test Arrangement for Measurement of FM Sidebands
2-9 Sensitivity of 30 mc Crystal Oscillator to Vibration
h0-3
2o
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42
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50
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51
atress 62
Sensitivity of 30 mc Crystal Oscillator to Power Supply Ripple 63
Solid state Por Amplifier
2-12 Maximum Sideband Amplitude w
Eccentric Deformation
FM Sideband Amplitude with Respect to Carrier
Length Variations
2-14 Preselector
2-15 Pulse Decay in Preselector Filter '16
-16 Second IF Converter 79
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br nd Converter
on Semencing
Functional Block Diudram
trtbutiOfl with Multiple PowerSupplies
Same Unit
bation Wiring with
e Units
' Trave Wave Antenna
Supply Feedina
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1. INTRODUCTION AND SUMMARY
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1.1 INTRODUCTION
ihis is the first informal monthly technicei. report under Con
tract AF 33(657)-13264 and covers the period from January 17 through
gust 30, 1964. None prior to this report has been published. as
considerable effort ba been devoted to system analysis, and ystem
par eters of this project have changed rapidly. However, close per-
sonal liaison has been mmintained with. the Project Engineer and other
members of the customer's technical staff in resolving these parameter
changes and in maintaining up-to-date knowledge of project status.
Now, sufficient progress has been made in the analysis Of the
scIA,ve sub-system to document the decisions WhiCh have, been reached.
and to render informal monthly reports upon technical progress and
additional system changes which may occur. To accomplish this requires
a more detailed report, at this time, then is contemplated for the
usual informal monthly technical report.
1.1 ESTABLISHMENT OF TASKS
In order to establish technical and administrative control of
the contract the work being performed thereunder has been divided
into tasks. These have been grouped in three major categories:
a. Project
b. Active Oubsystem
? Antenna Subsystem
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Included under Project tasks are:
Project administration
b. System analysis
c. clutter flight test program
ineliied under Active Subsystem tnske are:
a, Active SubSystem Mechanization and Integration
b. Transmitter and Rio circuits
c. Receiver
d. Data processing
e. Uutter Tracker and Video circuits
f. Low Voltage Power Supplies and Special Test Equipment
a. Filter B:rnk and Interrogator
Included under Antenna Wsaystem teaks are:
a, Analysis and MOdel Study
b. Development of Elements and Power Dividers
C. fabrication and Test of Deliverable Antenna System
or this and subsequent monthly technical reports, project efforts
will be reported by tasks under these major categories.
1.3 won EVENTS
In summary, the major events, Which have occurred during the
period herein reported, are tabulated below:
a. Preliminary system Analysis (performed intermittently
from the issuance of the initial proposal January 18,
.1964 until verbal authorization to proceed was given
April 8, 1964. This was a limited effort for Which
anticipatory costs have been allowed).
"-
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b. equote or active subeystem and quote for antenna sub-
aystem on or about April 7, 1964.
Continued system analysis (April 8, 1964 to present
date).
Requote of antenna ubsystam y 8 1964,
eceipt of letter contract, Py 15, 1964.
t. Analysis of anticipated radio frequency interference
to operation and its effect upon operating frequency
power. (This analysis resulted in decision on or
about June 22, 1964 to change the operating frequency
from that oposed January 180 1964 and to double the
operating power and the consequent increase in the
scope of work outlined in document A181225? dated July
1964)
4mnizetion study, definition of subunits
liminery subunit des pp (April 8, 1964 to pre
date)
:eceipt of definitive contract and first amendment
thereto,August 11, 3964.
1.4 CONTRAC
and are not included within this repo
1.5 PROJECT TASKS
1.541 2.1e12.1....a.----t
Initially the anticipatory costs were considered to be those
accrued prior to verbal contract go-ahead on April 8 1964. This
effort was devoted to continuing system analysis from January 18,
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system parameters.
Additions]. efrort was devoted toward system mechanisation. A pre-
liminsrl
block diagram was developed and from this block diagram
preliminary sub-unit definitions were made. Further technical effort
ws devoted toward Investigation of clutter filters, filter banks and
preparation of technical data demonstrating that the performance re-
quired of these filters is achievable in the operating environment in
which operation is intended.
The total costs so accrued and charged to enineering task AMA
are approximately $190100, of which approximately $1,100 coats relate
to he passive system electronics and will be transferred to contract
(657)13262 which resulted from that effort and $3000 of which costs
relate to the passive antenna system and will be transferred to con-
tra AF33(657)13261. The $15,000 remaining costs relate to the
active subsystem and make up the anticipatory costs allowed unTer
Contract AF33(657)13264.
However, under the definitive contract I sued August 11, 1964
anticipatory costa are defined us those accrued prior to May 26, 1964.
anticipatory costs so defined, consist of time and
materials accrued a Inst enlineering tasks other than AA1A between
April 8 4 and M4y 26, 1964, plus the $15,000 determined above.
illgineering Task AA1A was closed April 8, 1964, and no costs were
accrued to it stibsequent to April 8, 1964. Thus, under the contract
definition total "anticipatory costs'' to May 26 1964, for Contract
AF33(657)13264 are approximately $100,000.
Note: that all references to costs made above are based upon
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en1neertng department computations and are not offici1. Off Ic
compute. ons must come from the ecuntIfl Departit.e
1.5.2.
A 11 projec group has been esteblis
niatrative
technical control of this project the persons named below serve
time on the. project;
8'
Prozrem Manager and jDiftu7 Woting-
sentative.
ba 8, Wrray,ior ]nineer, as assistantto the
program
responsible for s ,glneering cost and
chedule control, technical reports, project security
and other edminiatretive aspects or the p
jt
3enior Engineer
project uneger, responsible for
ect
latent to the
-
1 coordination
of the project and mechanical liaison with the customer.
and with other contractors, responsible for releted
lystems.
roject group
the e functis vith regard to con
tracts 657)13261 and AF33(657)13262.
In addition, J. W. Stunte, Manager Aerospace Develo
N. 3mith, Aerospace Fmginnering Mane r Mr. V. 1etrou, VP and
General Mane Aerospace Division and P, W. Eby, Aerospace Marketing
Project Liaison, function with the project group on a part-time basis
In their respective capacities as required.
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1.5.3. Iteasat4ly.teui Ana els
Also serving the project, 3 ince its beginning and at the present
time upon an essentially full time basis, are 121_1_124w Advisory
4ngineer, radar systems specialist, and N. .Wheeler, Advisory Lrigin..
ccr, Antenna 4stems specialist. These have primary technical respon-
libility for the establishment of ystem operating parameters and
equipment specifications for a syatem fulfilling the operating re-
quirements established by the customer.
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1.6 MUSE .A/U=StS
A considerable amount of effort dories this reporting period has
been devoted to more detailed analyses of system requirements, baited
on new and gore complete customer input data. Furthermore, in a
bar of area., ways have been devised which improve performance beyond
that originally obtained. Also, a number of potential problems were
uncovered which were not previously realized, and have been circus!.
vented by modifying the mechanization.
1.6.1 rrempeney Choice
The most *portant single analysis involved a study of the effect
of transmitted freqpeney choice on the radar interference performance,
detection performance, and hardware physical Characteristics. Of these
the interference sources were by fur the overriding consideration. The
frequency band from 100-500 me was studied, which includes TV, high
power pulse radar, navigation aids, telemetry, and narrow:band communi
cations interference sources. The original proposed choice of 190
200 me fell in the TV band so a detailed analysis was made first of
the possibility of operating in the vicinity of both on-fregueacy and
off-frevency TV channels. To back up the analysis spectral measure-
ments were sada at a local TV station. A map of the geographical area
which would be negated by interference was prepared, and forestaly
Showed the hopelessness of such a frequency choice.
A similar study of operating in the vicinity of the known ti0010
of pulite radar was made, and the conclusions were similarly negative.
(le both capes the studies took into account interference spectra
antenna patterns, range variations, radar frequency hopping, etc.
9 k
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6.0
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tactical choice was
sources were less potent. Three
such bands were selected at 145 mc, 240 ma, and 360 mc as being repre-
sentative of the clearest regicms known (respectively, a hem band, a
telemetry band, and a communicatiorms band). Similar calculations of
interference problems showed that with *proved receiver design (to
be discussed subsequently) and with 6-10 ute tunability? quite acceptable
performance would result in any of these bands. Therefore, preliminary
hardwire designs at each of these frequencies were lade to compare the
detection performance, or more simply, to ccapare the hardware required
to obtain the same performance. It was found that considerable differ-
ences did exist, as Shown in Tableint. The low fret:pm:icy system had the
lowest power requirement and volume, but had an unacceptable frequency
tunability due to antenna bandwidth limitations. The huh frequency
system had excellent bandwidth, but was vex:" heavy and required excessive
power. The 240 me system was the best compromise, having adequate band-
width lowest weight, and moderate power requirements. Cowed to the
original proposed system however, it is somewhat larger and heavier
and requires more power. It was concluded that this is a email price
to my to gain the Improvement in interference 13meanity, and so was
recommended to the customer in June, 1964 and was accepted.
The system modifications which are required to be compatible with
the new frequency are:
1. The tranamitter average power must be doubled (to 2 101) to make
up for the sualler target cross-section and reduced antenna receiving
aperture at the higher frequency.
?
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2. The
yet fully sett
tion about the
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ation bee
ars that the propoaed symmetrical installa-
ine may not be possible due to excessive
spacing between antenna elements at the shorter' wavelength. If this
so, the two rows of elements must be mounted on the same side, of
enter, which causes more severe mechanical interference problems and
which requires the addition of a metal ground plena, behind the outboard
elements with obvious disadvantages.
3. The receiver must incorporate RP filtering and a smooth1y
shaped bang-snuffer pulse to reject the interference signals,. The
filtering is required to llelt the interference levels so that they
do not drive the receiver stage non-linear, causing clutter ipeetrust
preading due to in tion. The snuffer pulse shaping is neces
eery to prevent epectrumaliasing of out-of band interference which
would spread into the filter bank pastbead.
With the possible exception of the 4440444, none of these modi-
fications presents any problem of consequence the antenna problem is
ill being studied and more detail will be given later in this report.
1.6.2 Target Characteristics
Considerably more data has, become available from the oust:leer
gerding target characteristics, much of which has affected the 4.40,
tailed selection or web= parameters. The information obtained concerns
measured data of target cross-section siva function of angles and
frequency, computer plots of target velocity and acceleration versus
time for two target models sada range of target variables, , and 4 re-
vised vehicle flight profile.
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based upon *21
value of 3 met
As sem=
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ealculat
all the applicable
was thus used at 200 mc.
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of target re
flections. The
vallable, it was found that 3
was indeed a good design number for 200 mc but a deep null
170 mc and against 340 me.
This target data will be avilable for the next report
return is generally good in the 200 mc and 250 me
s are
d at
Another area of interest has been in radar return trom the missile
t. While there is a large amoast of information available,
ly frac Stanford *march, the results appropriate to this
on must be inferred. The principal problem is the lack of
rements from the frontal aspect. There is an exhaust return having
doppler velocity but its ma itade can only be estimated. at 10
2
meterr 4. 10 db. For this reason, this return has not been included in
the design work.
The new data on target veloeit and acceleration versus time con.
tours also are encourgeging in that they' are less severe than the
original proposal assumed. These data were converted into the minima
e veloeitw and the time available for detection as a fanatics
of positton within the desired coverage contour. the available time
'was found to have a minimum at the maximum cross-range corner of the
contour of tram 1.49 to 1.97 seconds, depending on the target model
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assumed, or an average of 1.73 seconds. This is very helpful compared
to the 1.3 seconds of the nominal for the proposal, and permits getting
more looks (which were found to be necessary as will be discussed).
The new gr. coverage contour is also slightly more favorable
in that it le someahat smaller than that amused in the proposal. All
of the vistas calculations, including the above times, are now based
on this now contour.
1.6.3 Antenna Coverage
In the proposal the antenna_ pattern was itemised to be a fan beam
shape. A tam/matted azimuth beam.width of 900 and receive of 45? with
a 20? elevation beam-width was considered. In the geometry of the
problem, the antenna pointing angle in elevation was selected to be
22.1/2? below the horizon. The receive beams were squinted 224/2?
either side of the vehicle axis.
To check the coverage of the required area, a detailed study of
the gein pattern was performed. With this small elevation pointing
angle, the pattern is distorted from a fan beam because the antenna
operation is approadting endfire condition**
As has been mentioned, consideration or a different antenna
con-
figuration was also reqaired due to the frequency change. At the now
tranmaitted frequency, the symmetrical configuration proposed could
only be, medhanised with a spacing of approximately one wavelength be.
tveen the rows of the array. An aegmmetrical configuration is needed
to reach the desirable 0.5A. spacing.
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1.6.3.1 Clain ttern Investigation
Rsenination of the gain pattern of the array w
synthesizing the theoretical pattern fres the array
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known to be generated assaying a flat ground plane. The pattern va
then projected onto the earth plane for comparison with the desired
coverage area.
Two undesirable effects were noted in the one wavelength spacing
First* the main lobe receive pattern beam-width was ea=
This de satisfactory coverage of the required area more cliff
The second effect was the appearance of a sidelobe only 3 db
down fras the min lobe and located on the opposite side of the vehicle
tion with such an existing eidelobe could nullify or con-
fuse the sense of detections made by the system.
A similar examination of patterns for 0.9A spacing was also con
ducted since it was considered possible to attain that spacing. The
results were not significantly different owever.
Inspection of the element receive pattern,
cause of the beam-vidth change and aidelobe generation* revealed that
a O. X spacing is optimum. Therefore* the process of synthesizing
gain patterns and cowing them with the desired coverage was repeated
for this case. The wider beam-width eased the coverage problems and
as expected* the sidelobe level was reduced to a negligible factor.
Because of these factors* the use of the 0.574- spacing* 1...* the
asYsmetrical antenna configeration, appears most desirable for good
system performance.
The aayeasetrical configuration* however* introduces another
factor into the problem. Installation of the array an this configersti
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would cause both rows to be placed on a plane inclined 1 in roll.
The resulting off.center transmit pattern is undesirable and the
tonna patterns must be intentionally distorted in order to make them
ymmetrical about the vehicle axis. A planned variation in the element
design will accompliah this and will be described later in this report.
Figure 1.1 Shows one-half of the coverage area on the earth with
2-wny gain contours superimposed. These contours were drawn for the
0.5 separation array mounted on the inclined plane. The dotted con-
tours on the figure are desired gain contours generated from detection
probability and eclipsing loss considerations as described in a later
paragraph. The figure Shows that satisfactory coverage will be obtained
with this antenna configuration.
Note that the contours in figure la are Shown in db below t-vey
peak gain. The two-way peak gain of the antenna system has been
calcu-
lated to be 25 db including all antenna losses. This has increased two
db from the proposed value because of more precise pattern and bean-
width information.
1.6.3.2 PI-tainting Angle and Beam width Investigation
Pointing angles and beam-width were varied to determine the nraaer
values throughout the gain pattern investigation. Some chan
wired to reach the pattern shown in figure 1.1.
The transmitted azimuth beam-width remained 90
value Changed to 45?. In elevation, both receive and tranem
widths became 21-1/2?.
It should be noted that the beam-width figures voted exist only
-way figures. In the synthesis of the 2 dimensional two.iway
n
,
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patterns, due to
tion planes are twisted
ing.
0200260001-7
line is34?, while a 20
1.6.3.3 ummar/
ge investi
ould be 0.5
the
ambigity. Present calculations proceeding with the assumption that
an 'symmetrical antenna configuration must be used to reach this condi-
tion. It is possible that the alternate symmetrical form can be used
if a method can be developed, to shorten the electrical 'separation of
the rows.
Use of the 0.5 ?, *Pacing and the new poi
patterns which appear to satisfactorily cover
i.6.4 Integration Time
Of all the parameters, other than the an
dimensions lose their mean
elevation were changed
measured from vehicle
anale was selected.
coverage and
a
of
e of
a
d area.
optimization, the selection of the integration time is probably the
moot important. There is only a short time available in which to make
a detection, verify that it is a desired target, and reject undesired
targets.; in the meanwhile trying several Pars so as to prevent eclipsing,
and selecting the best transmitted freqpency to minimize interference
A study was made of the effect of integration time on the signal/
noise required tor detection. Shorter integration time is partly made
up by having time for extra looks, but the longest possible time was
always found to be best for detectability. When the effects of false
r
Approved For Release 2001/08/28 ciA7Rpp67p0o6$1. 00200260001-7
tva*A
Approved For ReleasiSpEt
0200260001-7
targets were considered, it was found that at least 4 looks are neces-
sary to prevent possible missing of a true target due to the pur
ing 'sequences in the presence of a false target. Also, a study of the
effect of having the radar looks not exactly synohronized with the target
available time showed that a considerable loss resulted unless at least
four look times are allowed for.
The integration time also influences the scanning loss that ze-
suite
when the true target acceleration does not exactly match the
filter bank sweep rate. It also directly affects; the filter bank move-
ment of the target from one look to the next and hence the discrimina.
tion performance. The former effect makes a short time desirable, while
the latter makes a long time desirable. All of these effects were calcu
lated and compared, and an integration time of 0.29 seconds was selected
as the best compromise. This permits 4 looks as shown in figure 1.2 in
virtually all cases including even the worst of the target models and
reasonable performance in all the areas mentioned.
1.6.5 Filter
The choice of filter bank parameters are also impo
ing the detection and discrimination, perfornrnce. The
were considered of the choice of band-width of the mdi
filters. The most important one is the discrimination
desired and false targets. The narrower the band-width
number of filters the target moves from look to look. An analysis
the centroiding error in determining the target average filter position
showed that it would be at nowt 1/2 filter, corresponding to 4, 1 filter
ermneut error from look to look. Since this error is fixed, narrower
filters improve diserimination.
hi
Approved For Releas'
0200260001-7
4
Approved For Re/Erafrept 8/28 : CIA-RDP67B00657Rt300200260001-7
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Approved For Release
use of
ould result, how
targets which
nine loss results
improve d for detection
in the filt
ction integration. A serious problem
rrow filters were used, due to true
tehed to the filter bank scan. A scan
d effective integration time. This is
is a minor at.
especially true for target signals that happen to fall near the split
between two adjacent filters. Curves were made of this loss and the
narrowest filters which we acceptable loss were about 14 cps at the
c s points. This choice results in the acceleration acceptance
band of figure 1.30 due to centroiding errors, Which seems qgite reason-
able. This figure is for the worst possible 3/N and the average curve
Is much sore nearly square.
The total band-width covered by the filter
om the clutter edge up to the highest target velocity of
It was found, hovevers that the upper edge is not at all critical, only
affecting the maxim= number of looks near zero azimuth. Beyond about
5 looksvery little is gained in detection performance, so the filter
bank coverage was selected as 360 ape which gives at least 3 looks for
all conditions of geometry. This reduces the number of filters somewhat
below what would otherwise be needed, vhiCh is desirable due to the nar-
rower filters now required..
The frequency response of the individual
originally a 2-pole 1mtterworth response. The effect of a very strong
false target was found to be to trip off a very large number of filters,
due to insufficient skirt attenuation. A study of maximum signal levels
cover
Approved For Release 2001/08/28 : CIA-RbP67B00657R000200260001-7
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0001-7
and filter cosplextty resulted in the decision to gp to 3-pole flutter-
worth filters Which units the number of filters tripped to * value
the digital centroiding circuits can handle, while also greatly retic-
lug the portion of the filter bank which a felse target can mask. These
factors appear to definitel
filters.
The
filter re
outweieh the additional complexity of the
.b point for one filter to .over an adjacent
db level orieinal4
was found to be less than the
assumed for two reasons. First, the detection performance is much
poorer for a signal falling at this point even thoueh there are two
filters which cumulate detection. Becanely, the filter bank meehaniza-
tion can conserve on crystal elements by tag them in adjacent filters
but the cross-over is then pre-determined and. is -1.5 db for the 3-pole
filters. This then was selected as the new cross-over to satisfy both
desires, but, or course, is reflected in increasing:the total number or
filters.
In studying what is required to min
goals on the radar performance, it was found that a large dynamic range
is desirable in the doppler amplifier right up to the filter bank This
restriction limits the gain which can be used ahead of the filters, and
hence raises the gain required after each filter. 7his was found to be
nearly 90 db of gain in each of 30 filters and, furthermore, each ampli.
tier must be gain controllable for AGC and must track the others perfectly
This Was concluded to be impractical so a filter tank mechanization was
devisedvhich lutes only 1 amplifier which is time multiplexed between
the 80 filters hence gettbe;perfect tracking The hardware savings is
small, however, since the switching circuits nearly make up for the am.
plifiers saved.
Approved For Release 2001/0/28 :,t -RDF'078006FR000200260001-7
4
Approved For Releas
200260001-7
1.6.6 PH F and,DutY CYcale,
Teo factors forced the Is to be increased over the ropooed
Pint, the doppler spread of targets increa d due to the higher
transmitted frequency, requiring a higher par to prevent ambiguity.
Secondly, a new type of ACC was found to be necessary (to be discussed
subsequently) Which requires a clear band of doppler in which no target
si ls can appear. This requires raising the PRP even further. At the
same time it is desirable to select the PH? ratio so that bad eclipses
are avoided, and to position those that remain to fall at ranges where
the in, range, and available time are not worst. A. a result of such
a study, the Pars were selected as 7.42 KC and 6.36 KC, which satisfies
11 requirements.
The effect of tra
was found desirable to
ole was
pulse
pulse duration eqgal. Because of a small dead
of the receiver BF interference filter, this turns out to be a trens-
nitter cycle of about 0.48 rather than 1/2.
1.6.1 11101Se
Enceuse the antenna configur&
d it
to the ringing
not completely firm at this
time, rather than calculate the system tion performance for the
antenna,actual the reverse has been done and the desired antenna pa
tern found for an assumed level of performance. Figure 1,4 Shows the
result of these calculations, over the ground coverage contour, to give
90% probability of detection (and discrimination) on the worst target
model with the worst losses. In order to obtain this curve, all of
the known losses in the signal processing had to be first evaluated
such as the scan loos due to the signal moving through the filter bank
Approved For Release 2004/66/28 : CIA-RDP671300657R000200260001-7
Approved For Release
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Approved For Release 2001/08128: CIA-RDP67600657R000200260001-7
9 Approved For Release 2001/
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0001-7
signal loss &te to the signal falling at the filter bank cross-over
misaligned looks relative to the target available time etc.
the eclipsing was taken into account at each range, as well as
the number of look times available.
Present indications are that the antenna can give
gains over the entire contour. The two regions which are ust marginal
as expectedo are the maximum cross ranee corner region of the coverage
ontour, and the maximum range zero azimuth region. All other regions
should have considerably better performance since the antenna in
margin will be greater.
In the process of calculating the ON
required for a gtvea per-
force, a favorable error was found in the cumulation formulas given
In the proposal for multiple looks and this was pointed out (wad cor-
rected) to the customer in an informal memo in February, 1964. Curves
have been prepared for the per look and multiple look probabilities
versus ON for various conditions of eclipsing, and for various points
on the filter tank filter response for the new system parameters.
1.6.8
A number of mechanization trade-offwere considere
fluence system performance independently of the hardware
Several areas were found to give inadequate system performance and
were subsequently modified accordingly. One of these was the AOC system
which was originally conceived as regulating the signal-plus-noise ahead
of the filter bank, as past systems have done. This was concluded to be
unacceptable in this system since strong false targets, as are likely to
be present can easily capture the AOC and submerge the desired targets.
him-
Approved For Release 200008/28 :,CIA-RDP67B00657R00020.0260001-7
Approved For Release 2001/08/28 : CIA-RDP6713006671R000200260001-7
filter k. A
system was devised whieh operates on an out-of-band freauenci
to prevent target suppression. By applying the AGC after the
bank, coloration of the interference is prevented solving that problem
too. The detection threshold, was tmerowW.easo by generating it from
Integrated noise, thereby cancelling component drifts.
The new AOC also eased the clutter filter requiements since
clutter does not need to be completely rejected in the third IF any-
more as it cannot affect the new AGC. The wider dynamic range ahead
f the filter bank to minimize interference problems also eased the
clutter filter requirements, since spin the clutter need not be cum
pletely rejected. Both these effects ccabined make the clutter filter
no longer a critical item.
Besides the new AOC, a new
also been found to be deeirable.
of AGC
eaon
reliable angle indication, since it appare
chanization
reseed the need
s a crucial part
of e alarm. As a result, the original mechanization has been modified
to give a more reliable 4edication. The problem with the original is
that a strong target can give both a"right" and "left" indication even
thoizi it Is clearly left or right by exceeding the threshold in both
channels. A very simple modification has been made which now makes an
amplitude comparison on a filter-by-filter basis each look, using a
differential threshold. This will inhibit the wrong channel on strong
targets, while still giving a both indication when the signals are
pproximately veva. (At the customer's request, only two indicator
lights will be used rather than three, since "right" and "left" being
Approved For Release 2001/08/28 : CIA-RDP67600657R000200260001-7
Approved For Release 2001
lit
improved angle
factory, requiring aboQt 3..4 db signal amplitude differential to oper.
ate.
1.6.9 Miscellaneous Malyaes
A number of analyses were made to select the more detailed system
parameters. For example, one covered the choice of IF frequencies and
local oscillator frequencies for the receiver* Spurious sigmas can
be very serious in a doppler radar unless very careful selection is
made of the various frequencies. For example, each frequency must be
chosen to avoid intermodulation products of all orders from falling in
the pass bands and to avoid even very bigb harmonies of the radar m's.
Such has been done and Spurious frequencies should not be a problem*
Also, an analysis was made of the signal, clutter, and noise
levels throughout the system since these influence the gain distribution
and dynamic range desirable in the various bandwidth amplifiers.
The exact frequencies of lcumea radio sources in the world in the
band of interest were consulted in unclastified literature and exact
transmitted frequencies selected so as to best cover the total system
bandwidth while falling between the interference sources. A total of
7 frequencies were chosen as being adequate, an odd number being desire
ble for sequencing purposes.
A basically different type of "filter bank meebanization was
Wiled which appears to have some potential advantages in pertoince.
This mechanization would use a magnetic tape recorder to record the
doppler signals with a high speed read.head, and a single multiplexed
filter. A single filter would be adequate due to the time epeed.up
en
was calculated and found to be
0001-7
of the
e satin.
?
Approved For Release 20011081Z8 A.RDP67800657R000200260001-7
, _
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Approved For Release 2001108/28 : CIA-RDP671300657R000200260001-7
of
could be
supplier* if
relativeto write. Very steep and narrow filters
ilemerited with this arrangement. Tape recorder
contacted and all agreed on feasibility, but none conid
deliver in the required time schedule. Therefore, the idea was dropped
in preference to the original passive filter bank mechanization.
An analysis of the allowable frequency drift on each of the
crystal oscillators in the system was made and in the endeavor,
mechanization VAS devised which completely cancels all drift in the
first two local oscillators. In all cases the drift requirement* are
within the state of the art.
1.6.10 Clutter Spectrum Considerations
During the proposal stage, a value of reflection coeffic
was used which had been developed by extrapolation of existing
The clutter spectrum was predicted by manipulation of an idealized pat
tern incorporating the extrapolated cc;.
In Section 1.6.3 antenna gain patterns are mentioned which were
synthesized from known antenna parameters. These same patterns ziNr
be utilized to calculate the clutter spectrum more precisely than dur-
ing the proposal phase. This work is now underway. preliminary in
dications, using the extrapolated 6:1, are that clutter will be larger
than predicted.
However, in the interim, acme further data on reflectivity has
been secured. Fire
are plotted versus frequency.
in the proposal phase to pred
proposal. Later data from studies done by AHL provided the boxed points
at 428 mc.
P
a data. Values of de,
3. Mac were utilized
d point. at 415 en in the
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10
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Approved For Release' 2001/08/28: CIA-RDP67009657R000200260001-7
'
used, it would.:
erfored by the
bval seem% provided the
extrapolation shown by the
theta; varies between
ion predicted -12 to
-24 and -32 db at fa. The proposal extra
28 db for the same down-look e014100 (409 and 109 respectively). Taus
it appears that os may be substantially lower than predicted. On the
other bend the linear extrapolation is of doubtful value, as evidenced
by the slope variations seen on the curves. Also, little data was
found on other types of terrain (risme 1.5 is data taken over water)
and ground targets should place more stringent requirements on the
system.
In surnary, new calculations indicate
except that cr values may have decreased
clutter flit test (see Section 1.8) will sh
which will settle the question. Final clatter spectrum levels and
shape will be calculated as soon as the fli t test data is available.
1.8.11 lable of Parameters
Because of the various factors discussed above, many of the radar
parameters have been changed somewhat since the proposal was submitted
in order to better optimize performance against the updated threat model.
The present parameters are summarized in Table 1-2.
as
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SCryApproved For Release
Teble 1.2
1. ter frequency (f0)
2. Number of se1ectb1e frequencies
3. Spread of seleeteble frequencies
4. Exact transmitter frequencies:
1) to - 4,5 ma
3) to - 1.7 ma
(5) fo 1.6 me
(7) to 4.5 me
i ft:3 - 0.2 mc
2i fo . 3.5
4
a, 6 ta + 3.5 ach,
5. Sequence of RF frequencie
6. Avera transmitted power
7. PRF's
a. PET clock frequency
9. PRF dividers
10. Transmitter pulse width
11. Transmitter duty cycle
12 Peak transmitted power
13. Transmitter os/omm ratio
14. NUMber of receiver channels
15. Receiver amplifier frequencies (c
RP ano
First IF
Second IF
Third IF
Receiver elifier bandwidths
RF amp
First IF
Second If Third. IF
Approved For Release
00260001-7
242.1 mc
7
9 mcis
1-4-7-3-6-2-5
2 KW
gi fl #2
= 7.42 KC
KC
424,640 cps
(1) 32 x 7; (2) 32 x 6
5.45 usec; (2) 64.25 usec
(1) 04480; (2) 0.477
(1) 4.17 KW; (2) 4.20 KW
*125 db
utter edge):
2
OP
07P0,0.$57R000200260001-7
Approved For Release 2001/08M CIA-RDP67B09857R040200260001-7
17. Stale cry
104.2445 me
106.3945 mai
108.7445 me
Illato
.7445
5
11;
es:
6443 me
2445 me
15. Second LO crystal oscillator frequency:
19. Clutter track variable c
20 irci to
21. Clutter track eryte1 as
22. Local oscillator frequencies:
23.
First LO
Second LO
Third LO
RF amp
First IF
Second IF
Third IF
en
890.4 kc/s
Iter bank sweep
975.36 hei
29,111 mo
28.13664 isc
890.4 ke/s
filter bank sweep
15 db
0 db
40 db
70. db
24. Receiver internal noise figure 4 3 db
25. System noise temperature (at antenna terminals)
26. Receiver sensitivity 156 dhm
27. Maxim= clutter/noise spectral density into receiver - 70 dbm
28. Maximum CW interference into receiver (3 mc 32 dbm
0000 iC
29. Maximum input for 1 usec receiver recovery
30. Maxima intermodulation products
31. Bang snuffer on-to-off ratio (2 stages)
32. Sloughing snuffer:
Leading and trailing edge Shape
Rise or fall time
dbm
in 17 ;Ps
0 db
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Approved For Release 200
33. AGC 4mc range (2nd and 3rd IF)
34. Clutter track oscillator frequency off
36=
Linear
Ground
Clutter track oscillator stability and linear
Amber of filter banks
Naber of filters per filter bank
Filter bank bandwidth:
Cross-over
db
Noise
39. Ntanber of poles per fil
40. ota1 filter bank cover
;60001-7
TO db
0 epa. over range
2
40
14 cps
16.2 cps
17 cps
tervorth)
560 cps
41. Filter bank spacing ram clutter edge (at sweep start) 100 cps
42. Filter bank sweep excursion
43. Post detection integration time
44. Post detection integration samples (
45. Receiver blanked time between looks:
PRP settle and AGC settle
AGC settle only
46. ota1 tine per look:
No detection on previous look
Letection on previous look
47. ?else alarm number (Mmrcum's N)
48. False slam time (average):
Per look (noise only)
Verified detection
Verified detection
two looks)
N)
two looks)
aloe target
81 cps/0.34 sec
0.29 sec
5
0.1 sec
0.05 sec
0.39 sec
0.34 sec
106
l5inntea
10 years
75 minutes
Approved For Release' 2'0 110 A- B.M.:--Rtie0200260001-7
49.
50.
53.
54.
55.
56. AGO range of filter bank multiplex eiUfier
57. Maximum number of filters exceeding threahold:
Approved For Release 2001/08/28 : CIA-RDP671300657R000200260001-7
ired for
at 50% 50% eclipse a
at 0% - 100% eclipse 2-3
- 100% eclipse, plus, true 2-4
50% eclipse, plus true target 2-5
lea scanned
nee rate
6.36 kohl
84
75.7 clog
of sequences per integ&ation time 22
bank instantaneous dynamic range
er bank driver
er bank multi lex s1itier
of AGO filter
Strong true target
Strong false target
e target look-to-look filter - centroiiacc
movement
59 False tariffirt look-to-look filter - centroid
rejection movement
60. Multiple target filter
movement for inhibit
61. Angle quantizing
62. Alarm indication
63. Alarm duration
64. Navigation input
Quantization
Maxim= range
Data rate
40 db
20 db
560 cps
4- 10 to - 30 db
3
10
left, both
audio tone
30 seconds
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Approved For Release 200
65. Power supply voltages and curr
+ 42 V e 0.64 astps approx.
+ 22 V e? 1,72 mos approx.
+ 12 V ft 0.91 argis approx.
+ 6 v e 2.49 amps approx.
+ 6 V sgt 4.00 anus approx.
- 14 V 1.93 gunia approx.
v 0.83 amps approx.
- 28 v ot 4.50 as approx.
azimuth beamwidth:
Transmit
Receive
67. Antenna elevation
Transmit
Receive
63 Azimuth beam pointing angle:
Transmit
Receive
69. Elevation beam pointing angle (from antenna axis):
Transmit
Receive
70. Antenna peak in (at pointing
Transmit
Receive
71. Antexa Br bandwidth2 db)
72. amber of rows at aisments in antenna
73. 'Dotal number of antenna elements
900
two
4. 20?
11 db
14 db
* 9 =cis
2
2 x 17
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Approved For Release 200V
1.7
lop
led in the vehicle as three
60001-7
The electronics will be in the right side equipment box between stations
479 and 565. If the problems created by full wave.length spacing can
be resolved, the two antennas will be in the wiring troughs on each
side of the vehicle between stations 479 and 720. Interconnections
between the right and left side will be made through the wheel well.
Since the transmitting antenna and the electronics will require a one
inch diameter interconnecting coaxial cable to handle the high pow
the transmitting antenna will be on the right side to limit the length,
of the 1" diameter cable that in required. The left, side antenna serving
:s receive only, with no high power requirement will require u smaller
diameter interconnecting cable.
1.7.1 Antenna
The antenna
dielectric material
sheet will replace the trough covers and, be made the thickness required to
satisfy structural requirements. On the Sheet will be a series of boxes"
7 inches vide x 14 inches long and 2 inches deep. These "boxes" will be
spaced on 15 inch centers and When Installed will insert between station
frames. The 2 inch height of the box will enable it to stay below the
top of the station frame members.
The boxes will be connected in series by coax table throu
con-
nections at the sides of the box. The deplemer and coax connections
to the boxes will be limited to 1 inch in height and increase the overall
width of the box to approximately 9 inches. It is anticipated that this
will cons
a roe
sheet of
ly 21 feet long by 11 inches wide. This
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Approved For Release 2001/08/28 : CIA-RDP67B00657R000200260001-7
approach will permit the box interconnectioncables to go under the
trough area. This will
allow the entire assembly and diwassimsbly of each antenna in one piece.
1.7.2 Radar Electronics
frames which are recessed
.10 inche
The radar
ctronics will be installed in the box structure sup
plied by the user along with the RF parts of the right side direction
finding (4.f.) antennas and the cooling system. The box will then be
installed brougha UAW door and bird mounted to the airframe
The d.f. RF parts and the cooling system will be hard mounted to
the inside or the box however, there will be thermal insulation Inserted
at each mounting point.
Except for the filter x the entire
tion isolated from the box. In fact, the transmitter-re
have dual isolation from the box.
The radar electronics will consist of five separat
wIll assemble through the box cover onto the vibration isolation system
using standard military electronic equipment clamps (RAO-573)? These
fasteners will permit the assembly and disassembly of the radar electronics
without the use of tools of any kind.
The five chassis are the power supply, transmitter-receiver,
clutter tracker, filter bank and the data processor. A list of the
weight volume and power dissipation le Shown in Table 1-3.
vibra-
Approved For Release 2001/08/28 : CIA-RDP67600657R000200260001-7
Approved For Release 2,,
TABLE
SYSTEM
,L-RA
1
ALING
P67B00657R000200260001-7
i
vow
V
,D S
pNIT
Power Supply
61+
1.6
360
Trans-Receiver
89
2. 2
P081
Clutter Tracker
18
0.4
55
Filter Beak
10
0.4
Data Proeeanor
13
0.5
10
Frame & IntereoluiectIons
35
Total 229 Lb. 6.4 262(
;sOLA
Approved For Release 2001/08/28 : CiA-KDP8-7"B00657K000200260001-7
Approved For Release 2001/08/28 : CIA-RDP67600657R000200260001-7
Cool.
of he cooling system indicates th.at up, to
chenjer units will be installed in the upper
of the box. As of now it is intended to use
filter and. heat exchanger units that are
other system 14.1 the box. It is intended
O watts of the 2627 total Chown in Table liquid directly. The fan-heat =hanger units
used to elimmnnte the remaining power dissipation, environmental
nci tag system load.
The 25000linr fluid will enter the rear of the box through a
connection, pass through the filter and go in parallel
through the fan-beat exchanger unite. The fluid will then pass through
the power upply chassis to cool the high voltage components and the
low voltage regulator power transistors. rrom the power supply the
fluid will go to the tranamitter.receiver to cool the limiter, power
tube and duplexer. From the transmitter-reeeiver the fluid will be
pumped out of the box through another self-sealing connector.
Calculations indicate the fluid will have a 60PF temperature rise
in the box and assuming a 95?F inlet temperature will result in a
outlet temperature during radar operation.
Approved For Release 2001/08/28 : CIA-RDP671300657R000200260001-7
Approved For Release 2001/08/28-: CIA-RDP67B00657R01,0200260001-7
1.8 cuirm FLIGHT TEsT ixi
1.8.1 zose
To determine the radar reflectivity of various types of terrain
in the 200 mc. region. The terTain to be evaluated includes flat
land, two aspects of a city, a bay, forest and mountains.
1.8.2 Oeneral Description
In the initial planning, the company
a to be utilized
for the flight pregrami. As this aircraft was sold before the tests,
a Becchcraft of the Queenair type was modified for the fli
ts.
These modifications included structural additions to mount a vertic
polarized antenna on the right side of the aircraft and to mount the
transmitter, receiver, display and recording instruments within the
aircraft.
A Navy type SIC radar transmitter was used. To physically fit
in the aircraft it wau cut into two parts and rewired, The Vitro
model 1306 receiver was also modified to remove all coupling time
constants,
A mockup of the antenna reflector portion of the aircraft's
surface made- to facilitate the measurement of the antenna pattern
and gain on the antenna range. The aircraft structure and equipment
modifications are completed and the system is in -operating condition.
The first data flight baa been made with the radar equipment
uperatin, satisfactory. This data plus that from additional test
flights will be processed to determine a median value of reflection
coefficient for each type of terrain. If possible, the results will
be compared to results of similar tests run at other frequencies- by
Approved For Release 2001/08/28 : CIA-RDP67600657R000200260001-7
Approved For Release 2001
the Naval Research Lab ML) and atanford P
Ae o ledgment must be made of the ideas en
m NPL and. SRI. project reports and partic
Mr.L. tJ. Ouizrd- of MRL.
1.8.3
nt
iir aircraft
dar tranmaitter
model 1306
poration
60001-7
h Institute.
echniques derived
ly from a visit with
el ?10
Du cad - Bird model 82A
Airborne Instruments Lab power oscillator type 651
rz1ine wattmeter moue' 611
Tektronix oscilloscope type 545
Blue bard duplexer for type SK radar
forti 14 polarized side looking antenna
Camera
Procedures
abe procedures used in operating and calibrating the system and
measuring and processing the data will be described brLefly here in
terms of the conduct of a typical. flight. The specific procedures may
be conveniently divided into throe groups: preflight cheeks on the
calibrations and measurements durinG the night and post
flit data processing
During the initial calibration of the system on the ground, the
1,,ran.. -Ater is tuned to operate on the assigned frequency of 219 mc.
and the pulse length and peek radiated power- are accurately determined.
Approved For Release 2001108/28: CIA-RDP67B00657R000200260001-7
Approved For Release 2001/08/28 : CIA-RDP67600657R000200260001-7
For initial calibration? the system is connected as indicated in figure
1.6. The deplexer is terminated with the dummy load and the limiter
end switch. The transmitter and duplexer are then tuned_ to 219 me,
To calibrate the peak power output and accurately determine the
pulse length, the :system is conneted a2 indicated in figure 1,7.
The duplexer is detuned and utilized as an uncalibrated directional
coupler. The type 651 oscillator is set to operate in a CW mode and
the oscillator coupling adjusted to give a 10 watt output. The trans.
mitter output is then measured by comparison to the calibrated 10 watt
throu
kit
use of the variable attenuator, and the exact -pulse
duration determined on the detected pulse on the oscilloscope. If
possible, the return from a stationary target will be maximized by
tuning the duplexer with the antenna connected to the system as shown
In figure 1.6. Thia completes the preflight calibrations and measure-
in flight, the receiver will be tuned to the transmitter frequenc
end the receiver gain will be adjusted so that 95% of the returns fall
on the race of the scope. Boughly 240 picture frames of data will be
tok(n for each type, of terrain. Immediately after recording the data,
the receiver gain will be calibrated at four signal levels provided
by a CW signal generator. The calibration will be recorded on film
and the signal level out of the signal generator will be 1 .mad. This
completes the In-flight calibrations and measurements.
Data_ processing will begin after the flight films have been de.
veloped. Individual frames will be projected on a screen or blank
wall for manual measurement. Vertical displacements will be measured
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1
Approved For Renee 203
EC
260001-7
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Approved For REfrease 2
5 R1700200260001-7
A
Q)
3
0!. ?
Approved For Release 2001/08/28 : CIA-RDP671300657 000200260001-7
Approved For Release 2001/08/28 : CIA-RDP671300657R000200260001-7
t horizontal diaplae
to a
desired do
etponding to time delays ia1cu1ated
anges which in turn correspond to the
libration data will then be used to
onvert the measured displacements in distance unit,' to voltages.
The median voltage return for each downlook angle will be determined
for each run. The expected downlook angular coverage is roughly 10?
to 60?. The median value is used instead of the average at the
ouggestion of NNL. Finally. Lila median voltage returns will be used
to compute the radar area
0
The
ordin
ML formula
g-17 02 2 A
recalved po
it of horizontal area of terrain
mean range to target area
tran mated (peak) power
antenna gain
wavelength
A aprximate horizon
o the echo came0
tributionsiill be
which all observed eon
ed directly rron the
-median voltage return. R will be obtained directly from the tine de-
lay of the return. P and will be measured directly in the preflight
calibration% 0 has beenreasured using the radar antenna and
a mock-
up of the aircraft on an antenna range. In calculating A, an e- ival
ea rectangular beam pattern will be used having a uniform two way
pattern_ equal in azimuth to the measured two way 3 db beam
ttcm and determined in elevation by the transmitted pulse widt
Approved For Release 2001/08/28 : CIA-RDP67600657R000200260001-7
Approved For Release 2001/08/28 : CIA-RDP67600657R000200260001-7
E
NIZATION AND
ign of the
inalb set forth in the propoisal. 3r1ef the principles
ZATI
PERATION
syetem is pro
the
Thaws:
A stable ItF frequency is t LnSIdttOd froze one antenna which covers
aln of interest ahead of the vehicle ground clutter
and re-
rom fixed velocity and accelerating targets are received on two
s relative signal strength being a function of their coverage
de of the vehiole. Two receiving channels are used, one for
4 one for right coverage. All returns not floppier shifted by a
ter than the vehicle velocity will appear in the receiver
of the clutter return On each receiver there is a fixed fre-
single clutter reject filter utich will attenuate this
about 0 db.
'Aro tee
this filter.
the titted frequency eay be adjusted in direct proportions to this
velceity to insure the unwanted doppler return falling within the reject
bond of the clutter filter. Although this is an open-loop technique it
is the one t often eieployed? end has received met of the design at-
tention to date.
In addition, clutter may be elose-leOp tracked by ptodically
eliifting sone of the clutter beyond the filter reject region to deve3p
enoujh error voltage to permit close edge tracking of the clutter re-
available to. keep the clutter pas
is available the vehicle velocity,
ned in
therefore,
Approved For Release 2001/08/28 :-CIA-RDP671300657R000200260001-7
Approved For Release 6
This second second technique will receive
months.
Any ridr echo received which has a velocity component toward
aching vehicle will be doppler shifted in exceee of the clutter
doppler and therefore will continue past the clutter reject filter to
the filter bank. Both fixed, veiocity and accelerating tergets are de-
. flowever, only targets accelerating a critical amount will d-
vcs the filter bank causing A second detection in *titers
d?aplcod A to 7it filter widths higher in frequency then their loc.-
tion
the first detection. The entire data processing hardware is
devoted todetermininz this critical displacement for alternate nlooks
sing a display of right or left alarm zone; concurrent with pro
ceosing all data to reject all ether rad-1r ethos not so shifted in
doppler frequency.
2.1.1
00260001-7
n in the coning
present b
bo viixed with a varia,
bet
following areas of change
eqeires that the clutter doppler
money to position the clutter in the fixed
equency filter. This tracktug may be achiered by varying the LO fre-
once, as proposed r the V s pr iously described for the current
izpi.Nither technique is satisfactory.
(b) The clutter track loop is closed after the third
edge of the clutter filter) inetead of through one of the
ter bank because the soothing reduces the duty cycle of the
oltage present in the filter bank where as the clutter frequency
Approved For Release 2001108/20 : PA-RDP671309657R0700260001-7
Approved For Re4ease 2
1 ?tz ...,_ I bl Nx-
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Approved For Release 2001/SFECMIP67110NCIN0001-7
Approved For ReleaSPECIALIP
0200260001-7
le undieturbed at the re.lect filter.
(c) The transmitter on-off time is determined by gating the
stalo Instead of the RF amplifier, thereby *laminating high voltage,
high power, grid modulation in the final amplifier.
(d) The IF frequenaes were changed to keep PR? hsrnioa
oC the paseband.
(o) The level of Janina interference is determined by monitme-
ing the third IF AGO which in turn is used to control the system fre-
quency diversity operation as disaussed in a follewing paragraph.
(t) An amplitude coeparisol circuit has been added to proven
chennel alarm for large signals in the following renner.
The data processor scans each filter bank to determine A left or
right azimuth target. If the target echo were large enough to be de-
tected In both channels the proposed data processor wild have made no
choice between left or right alarm. Therefore, the filter bank scan-
nine has been re-designed to inhibit the alarm from the weaker channel.
Figure 2.3 accompanies the following description of this circuit.
Zech filter in the bank is nore-destructively scanned twice during
the detector-integrator read out tine. During the first scan of all
40 filters the L'R gate is present and each filter in the left bank is
ceepeeed in amplitude with the corresponding filter in the right. This
filter-by-filter comparison results in a signal output pulse only if the
left bank amplitude exceeds the right. Beth banks are scanned eleul-
teneously 4 second time only now a signal output pulse is sent to the
centroid locator only if right bank amplitude exceeds left.
?
Approved For Release 200,11.08/2,8, c1,4-RDP.71300,611,1i000200260001-7
two
Approved For Release
,wreagirrox.
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Approved For Release 2kortow.48 : CIA-ROP67$00657R000200260001-7
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Approved ForReleaSpEpr3
2.1.2 e
lefore beginning a
00200260001-7
the eystem timing and sequence
el: operation it may be well to point out one area where present design
.:ioee5 depart freet the propose".
The proposal states, te,ten Ja:a or interference is detected a, search
ner e clear channel is made by the selector. Ir no clear one is found
the selector has menery which picks the frequency Which gave the loweet
level of interference. subsequently, a new search is made periodically
se,y- once a minute, until a clear chennel is found". The following tech?
nique is now believed to be superior, and has been included in the
eresont design.
Leven transit frequencies, each shifted About one megacycle, are
Available. The systeie will transmit on one frequency and ne for one
filter 'vex& integration time,. then neve to the next freqtxency and P,V
for the next Integration time. It will continue to switch between two
Pats as it alternately samples eech available RF frequency. tcthen trio
clearest channel is Ice ated the systen will remain at that frequency 'Alt
t1llelternately continue searching for a clear channel. Note that when
4-tit" (radar echo detected in the filter bank) occurs the seertee holds
the wale ilir and PRF for the ne4t look period. Fienues 2.4 and 2.5 Ines?
trate this sequence. Only five frequencies are shown instead of seven;
,Lre_i the events are explained in reater detail in the following paragraph.
2.1.3
The irovioue section with Flames 2.4 and 2.5 has explained the
sequence of operation as a fraction of Jam and target detection. This
section will prAricie additional detail. Figure 2.6 will be needed to
follow each step.
Approved For Release 20900012
719
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0260001-7
Approved For Release 2
0260001-7
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AppraVed For Release 2001/08/28 : CIA-R 67600657R000200260001-7
Ft yr.
1,3Arqic.
Approved For Release 202fel
Ditin
0260001-7
transient produced by the gate itself will not seriously
affect the system.
The AOC loop uses a delay (level threshold) and a time
sample-memory feature. The 4sample-store" function is tn-
plemented by an AOC detector having two different time constants
which are switched by a "sample-store gate pulse which is
originated in another part of the system,
Because If the potential size and reliability advantage
of integrated circuitry, use of Westinghouse functional blocks
Is being considered for most of the functions in this section
of the receiver. Preliminary circuits have been designed and
constructed for many of the stages and experiments have
demonstrated the feasibility of this approach. Detailed design
Is proceeding and a preliminary concept has been. reached.
!P10-11
,
Approved For Release 2001/08/28,: CIA-RPR671300667R000200260001-7
Approved For Release 2001/08/28 : CIA-RDP67600657R000200260001-7
2.4 DATA PROCZOSOR
The Data Processor serves as system operation sequencer as well
as performing specific functional. operations.
2.4.1
t.
blocks in
detectionstarget recognition proceeds simultaneouely with scanning
of the filter bank and does not impose a requirement on cycle time. The
symbols n and x represent flip flops.
2.4.1.1 Data Processor Fepctional Operatione
Functional operations performed by the Data Processor are described
with reference to the functional block diagram shown in Figure 2-19.
2.4.1.1.1 Timing Signals
The Central Clock Genera
ecrntrolied oscillator and generates various sub harmonics of the crystal
frequency through a binary counting process. Various states of the
counters are decoded for use as timing signals.
A set of four pulses is pent to the RF subsystem for each RF pulse
Either of two repetition rates are selected ,Nr this set
of pulses, One of the four pulses at the lower repetition rate is also
eent to the filter bank to control events during the integration period.
Another set of pulses synchronise the filter bank interrogator with
the cebtroiding registers the data registers and the data comparators.
Other clock pulses are provided in too great profusion to be shown in
Figure 2-19.
of
ted with an asteriek,
in flow chart
blocks, are
al cycles is
that processing of th
he
output of a stable crystal
Approved For Release 2001/08/28 : CIA-RDP67600657R000200260001-7
Approved For Release
i
F"
C.71
-
(LApproved For Release 200
2.4.1.1.2
G260001-7
As indicated he RF is: periodically switched
the yes tipg AGC voltage is compared with that obtained by use of the
previoAs1y selected RF. The ACC processor converts the analog ACC
voltage to digital form and compares it with the stored value from the
previous ewp1.. The RF selector contains two registers whish retain
identities f the currently selected RF and the next to be selected RP.
The Identity of the currently selected RF is transmitted to the RF sub-
system on 4 Hone-hot line basis. The same information is: tranemitted
to the, Velocity Matiplier Amplifier gain switches on a vone-hotu line
haste.
2.4.1.1.3
During filter bank inte
receives threshold detectio-
which are derived from euccesIve filter positions in the filter bank.
mlee occurs atter a string of threshold dotectIone a 1, is set
into a bit position in one of the data registers which corresponds to
the value f the count in the centroiding register. The centraiding
regIster is reset to zero and counting will resume with the next thres-
hold
detection. The bits in the data register are shifted in enchron-
itien with filter bank scan, Hence t the end of filter bank in-
the pattern of "Its" in the data register represents the
controtd values of the strings of threshold detections from the filter
s the
number of such detec
bank.
The cen
data at a proscribed
maximum count if the number of threshold detections in a string exceeds
the prescribed maximum number.
Approved For Release 200:08/28 : CIA-IRIDFi6714006`57R00 260001-7
Approved For Release 2001/08/28 : CIA-RDP671300657R000200260001-7
U ration of the ta Register 3elector (DRS) and Hit Eetectr (}
an be readily d by assuming that the first
ram the filter bank was obtained on the Nth interrogation. On all pre
ious cycles both PRF and RF were switched eachcycle as ndleat d in
igure Also, the DRS had selected data registers L (N) and R (N)
to reoeive centroided values each cycle.
On the Nth vele, at least one threshold detection as
the roided values(s) stored in L (N) or R(N). Ths Hit Detector the
causes the DRS to select L (R + 1) and R + 1) to receive data during
the next filter bank interrogation. Simultaneouslr,
PRF is inhibited. At the end of the (N + 1)et cycle
lection of L and R (N) for the (N + 2)nd cycle
are switched.
Centroiiing results in ntisation units half as large as those
of the noncentrolded data, hence the registers L (N) and R (11), which
atore data for ono system cycle, consists of approximately twice as
qany flip flops as there are filter positions in the filter bank. The
lengths of L + 1) and h (N + 1) are determined by data processing
criteria rather than storage requirements since data processing proceeds
simultanmAncly with the (N * 1)st scan of the filter bank. L + 1)
d R * 1) consist of apprmximately one third as many flip floPs as
(N) $Zb H (N).
Each coeparator circuit (lert and r a number of
g of 111? and
reverts to
h PRF d RF
ogic gates interconnected in such a way as to cietse
it patterns as the contents of the register L (N)
) and R + i)7 are shifted past. Target det
own in Figure 2-20,
ain prescribed
+ 1) for
n criteria arc
Approved For Release 2001/08/28 : CIA-RDP67600657R000200260001-7
Approved. Fszic?Retrase 2
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Approved For Release 2001/08/28 : Cl
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Approved For Release 2001108128: CIA-RDP67600657R900200260001-7
c.v.\ LI IIL .17E,
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? -
--\( -
Tar-et Criteria
A
D
C
D
Target
0
X
X
X
No
1
X
0
X
No
1
0
1
0
Yes
1
0
1
1
Yes
1
1
1
0
Yes
1
1
1
1
- No*
* To only if the "1" in D bears a specific relationship to the "1"
in C. Thus, for a "1" in position z in C the specific relationship
would be satisfied by a "1" in D only if it were in one of the pos-
itions indicated by the symbol y.
t r C) r" e C r \4 + e
Approved For Release 2001/08/28 : CIA-RDP67600657R000200260001-7
Approved For Release 2001/08/28 : CIA-R pqi 7 0200260001-7
2.4.1.1.4 Arm
In the evsnt that either co;parator c.r both detects a. prescribed
hIt pattern Alarm circuitry will be activated. If both left and
right alarms are activated as the result of the same filter bank in-
tion both alarm lights will be turned on and an audio tone will
'rated in the earphones of the crew for a period of 30 seconds.
one alarm in activated the corresponding light and the audio
ed on but the other alarm will be inhibited for the
durationconds of the first alarizi,
The block of Figure 2,19 labeled &1arm contains the 30 escond t
and the inhibit circuitry. Dux 3 contains the audio signal generator
and circuitry for conversion of signal level from that of the eyetem to
that of the vehicle.
2.4.1.1.5
The VMAC accepts velocity from a doppler navigation equipertt in
the form of a 12 bit binary word transmitted in serial with
4.4
r
significant bit first. Ones and zeroes are represented by positive pulses
on separate lines. Positive pulses simultaneously on both lines in the
bit position indicate end of transmiselon. Beth pule* amplitude
and ate width are converted to values compatible with wystem echan-
in addition
to the signal conversion circuitry, the VMAC contains
three 12 bit registers. 12 bit D/A converter, and some miscellaneous
logic. One 12 bit register receives the converted data fro the navi-
gation equipment. A second 12 bit register holds the digital value for
conversion. The third 12 bit register serves as an exchange medium
between the first two. Navigation data is transferred to the exchange
Approved For Release 20:01/08/28::70A-R6067B00657R000200260001-7
Approved For Release 2001/08/28 : CIA-RDP671300657R000200260001-7
register by the end of trart on signal. New data is entred into
the holding register only at time of RF switching in order to not put
transients into the :vat en. The miscellaneous logic assures that both
transfers do not occur simul aneously.
2.4.2 amtwaladka
The Data Processor will be,ethanized utilizing Int
d in TO-5 12 pia cans mounted on double sided printed circuit
The boards will be special purpose in order to increase the
packaging density.
2.4.2.1 givatta
4tcros1ectrontc Intejrated Circuits (MIC) are utilizedvherever
boar,
DTL. type MIC blocks were selected and are furnished by West-
inghous
lecular Electronics Divioion. The MIC blocks used are
'4,R213T, WM201T, WM211T, 210T, 4224T. The Data Processor uses apprem-
imately 500 12 pin cans of RIC circuits in addition to the conventional
noonents used in the 12-bit D/A converter and the 4-bit Nib converter.
2.4.2.2 ItIghaglim
The Data Processor will be packaged by utilizing ten different type
of printed circuit boards containing an average of 45 cans per board.
The block diagrams Figure 2049, is divided into boards as shown in Table
2.4.3 ItRaie,,t0JIAt
4bsystom Design 90% complete
Logic Thacige 902 complete
G. Layout completed for five Of the ten types of boards
D. Taping of one board complete
L. 3ubsystem test tool designed and being fabricated.
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IL
2
3
4
7
3
9
120
NAV FIDPEF;;;667twut
ordered for breadboard
?grated circuit, for bread
Table 2-2
Akr,o
60001-7
ector, Alarm Circuitry
Centroiding liegieter
Velocity Multiplier Amplifier (VW
V1-A D/A Converter
t, r
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a.5 CLUTTEi TRACKER AND nrso CIRCITIM
Clutter -tion
The clutter
mechanization is proceeding eubetantiall
planned in the proposal. The only changes of significance are
l) the digital velocity information-to-aes.log voltaot for the clutter
track oscillator, 2) the clutter track oscillator, 3) all frequencies
and 4) various gating circuits. In addition, the exact specification
or the clatter track audio amplifier will not be know until a better
model or the clatter is available as an outgrowth of the ritgra, tests
tn proigess.
2.5.2 Clutter Tr.ac_LiTszNevi tor Interface
In the proposal, the interlace between the external doppler navi-
gator and the clutter track VCXO las a stepping motor controlled 1)y
Lour wires from the doppler navigator. The stepping motor lott.4 t7techani -
catty connected to a potentiometer which les supplied with a D.C.
voltafp proportional to the transmitter frequency. 5uch a zuechanization
liroducea a D.C. voltage on the votentiometer arm proportional to true
doppler to control the clutter track VCX0.
Jubsequently, it has teen determined that chan in tb velocity
inforlation from the doppler navigator occur in real time; this
conflicts with the system requirement that oscillator frequencies change
only in a particular time slot set aside for Fatand frequency changen.
It is also desirable from a reliability standpoint to have an all
electronic interface.
The interface hes therefore been changed to a auted
converter supplied by a 12 bit serial velocity word as described
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Approved For Release 2001/88
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?
th the data processor section or tbis report. The analog voltage is fed
to an operational amplifier, the velocity multiplier, with, feedback
controlled by the same lines which select the transmitter oscillator
fr,quenetes. Thus, the output of the velocity multiplier is eqpIveIent
to the voltage at the arm of the potentiometer in the origina mechaniza-
tion with the important exception that it is now buffered from
unaynchrontzed changes in velocity data.
treicsItzlEaE VCX0
The mechanization of the velocity track VOX? is the most difficult
part of the clutter track circuits because of simultaneous reqeirements
or linearity over a wide range, stability, spectral purity, and
vibration Input. The mechanization in the proposal obtained an output
aruunii 187 KC by beating a VCX0 and a fixed cacillator in the l mc
rmnge. Revised system reqeirements have chanzed the clutter track
VCX0 output to around 975 KC with the deviation remaining I.G KC.
A number of mechanizations are possible:
I. Direct generation
a. Open loop VCX0.et 975 KC
b. Frequency track loop
c. Digital control by selection of capacitors, etc.
d. Several open loop VCXO's in 915 KC range
2. Heterodyne generation
a. VCX0 and fixed oscillator in 15-20 me ran.
b. Audio VCO and fixed oscillator in 975 KC ranee.
Detailed eel cations for this VCX0 have been submitted to several
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Approved ForReleaseR
m71,4
00260001-7
suppliers. It is intended to select one external supplier end carry
a back-up program at Westinghouse uzing a different approach.
Method 2a appeared to be the best choice and a 20 mc YCX0 wae
built havinE: the required linearity; however, with the VCX0 In a
3tatham Chamber for temperature control, the long term etability
inadequate. Tet a have been discontinued on thia oscillator until a
choice of external supplier has been made, and the preeent effort is
toward perfecting a noiee measarement techniqee ao that data can be
obtained on eeectral purity (particularly) in the vibration environment.
2.5.4 Velocity 441.1pl1er
The velocity multiplier and saumnetion amplifiers have been designed
and preliminary tests made. The precision resistors have been ordered
and final tet e will be made when the reeistore are received.
2.545 Scan VeXO
The scan VCX0 specification has teen submitted to several sappliera.
This unit is within the at-of-az-tend no problem is anticipated In
obtaining it as a purchased part.
2.5.6 Fixed Oscillator
The 975.4 KC fixed oscillator specification has been sUbmitted to
several suppliersj and a design has been tested at Weetieghouse. No
problem is anticipated; the oscillator will be purchased externally if
the cost is attractive.
t
Preliminary designs exist on the mixere. A balanced transformer is
to be selected before breadboards are built. Work on the various filters
has been deferred.
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r 9
2.5.6
Clutter smsrum
Some calculations have heen made to e
ta
olish the audio amplifier,
track detector and i6tegrator requirements. These calculatioas, based
On idealized c utter spectrum and the proposed clutter filter response
shapes did not yield adequate informatioil to complete the design. Therefore,
when current studies, including flight tests, yield a more. accurate
model of clutter, the design will be resumed,
2.5.9 Gatin2pircults
The gating circuits for the third IF section of the receiver hAve
,,:een designed 4nd tested. The hoard containing these circuits is in
drafting. Gating circuit designs for the front end or the receiver
and for the transmitter exist but are expected to change from time to
time as the final form of the receiver and transmitter design evolves.
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Approved For Release 20
2.6 LOW VOLTAGE POWER SUPPLIE8 AND SPEC -r UflT
2.6.1 Low Volt.agerPower_palges
2.6.1.1 P.12110.E152-VALAle-cl-M9222E4
The basic scheme of low-voltage d-c power distribution has been
revised. Instead of having the unregulated power supplies in one
location with individual voltage regulators located in each unit, all
of the voltage regulators (with one exception) will be located on the
we pallet as the unregulated sources. This re-vision was made because
a total of d different voltages will be distributed to the various
units over 21 different lines, there being multiple users of moat of
the volta . Thus, with the present arrangement, only 0 separate
regulators are required Whereas 21 separate regulators would have been
required for the original scheme.
The basic principle that is being followed in the d-c power di
'0ution system is that each voltage source will be connected to each
unit by a separate pair of lines, one of which will be the ground return.
These lines will be shielded, twisted pairs with the shield connected
to the unit chassis ground at one end and to the power supply chassis
grond at the other end. Both power supply terminals will be isolated
from the power supply chassis. The common, or ground return, IL* will
be firiay grounded at the unit by connection to the chassis grokold of
that unit. This principle is illustrated by the block diagrams,
figures 2-21 and 2-22. It is believed that this method will reduce
crosstalk and stray pickup on power lines to a negligible level.
The one exception to the regulator location arrangement is the
data processing unit. The regulator for this unit will be located
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SApproved For Release 20
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within the unit Itself, thereby eliminating radlatton from power
lines carrying pulse currents that are typically found in digital
equipment.
2.6.1.2
A completely separate power supply, consisting of a trensformer,
rectifiers, and a regulator has been designed for the sole purpose of
providing d-c power for the crystal ovens. The primary a-e inpat to
this supply is the 3-phase ac line so that this supply will be
energized whenever the ac power is present. This will permit oven
warm-up sufficiently in advance or actual system operation.
At the present time, the intention is to use no passive filtering
between the rectifiers and the regulator inputs (other than transient
voltage spike suppressors). The voltage regulators designed for this
system have greater than 430 db of ripple suppression over the frequency
range of interest. The regulators themselves will therefore be used
to provide active ripple filtering. In this nrer 8 filter choke
coils will be eliminated, resulting in a very considerable reduction
Of power supply size and weight.
The regulators will provide better than t0.2% voltage reanlation
over the full range of load currents, temperature, and norsa:' input
voltage specified. They will be completely overload and short-circuit
proof, with operation in the overlomd region between full-load current
and short-circuit clearly defined as to output current, voltage, aad
element dissipation for all values of load resistance down to zero ohms.
All overloads can be sustained indefinitely with no damage to the regula-
tore. Output voltage recovery tater an overload is completely automatic,
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and requires approximately 20 milliseconds. Each regulator wilt be
designed for a specific value of full load current; any reduction in
loud resistanee beyond this point will result in a reduction of both
load voltage and load current. Consideration has also been given to
the possible large input overvoltage transients that could occur. If
such a transient occurs, a circuit will reduce the regulator output
current to zero for the duration of the time that the input voltage is
above a given level. This level will of course be appreciably aboAAs
the normal operating range of input voltages.
2.6.1.3 Present of Low Voltage YomierAY.PO4.?
The basic circuitry to be used in all of the voltage regulators
has been developed, and preliminary tests have been made. The
component layout for the prototype regulator board* is nearly complete.
One of these prototype boards will be constructed within a week, and
more detailed tests of the eirc,Ait will be started at that time.
Information on the low-voltage power supply transformer requiremente
is expected to be complete within one week, at which time the -MM.*
former designs can be started.
2.6.2
cial ist E
I
A study has begun to deterldlne the detailed system requiremente
of the special test equipment. No detailed design work on this
equipment has been made to date.
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2.7 riLTEft BANK AND MERLOGATOR
The present concept of the filter bank reflects some changes
free:the originally propoeed system. These changes have resulted
nfter further studies of system requirements. Work is currently
eroeressing in the design phase as well as laboratory investigation
01: special techniques in the planned mechanization. Different pack-
aging philosophies are being evaluated to arrive at the best oechan-
ical configuration. Approximately 80% of the signals at the filter
nk interfaces are eoepletely defined.
The deviations from the proposed eysteal are categorised below
accormine to functional require:Ants of the signal processing equir
rant.
2.7.1
The number of discrete frequency detectinn channels for each of
the twe filter banks (left and right hanks) is now established At 40
instead of the originally proposed 25. Quarts crystal resonators will
be used in a 3,Tole filter having Putterworth Characteristics. The 3-
po1e ueharedo technique involves the Sharing of two of the three crys-
tals per channel with the two adjacent Channels. The bandwidth at
eroasover of adjacent filters is now 14 cps, and the 3 db bandwidth is
16.2 cps. The filter was initially propoeed as a 2-pole filter having
3 db bandwidth of 20 cps. The change to 3-pole filters provides
ereater reacaution of tares due to steeper skirts of the attenuation,-
freopency response.
A opecifications has been written for the crystals- and a purchase
order has been placed for crystals to be used in the breadboard oystee.
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t Ve;
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2.7 ?2
he echan1atiofl of a filter
ampli.fica of the f
detection requirementa and
the exb-
4O7 an mplifier and. Uetector in
different ph11oeopy h- been adapted in this eysten
rilter outputs and
ra1tip1ecect to sinE,1
intwator inputs of each
U detector par bank.
The advan pea of aPa31tip1exerd system are primarily improved tracking
stthility froLt channel to channel and feereali adjustments necessary.
le-off of linear network elements is a standard approach for 9WitCh-
inp
elements in the tailtiplexinr scheme and mx.y be cortaiderred as 4,An
antage because of reducei power consumption and lower componeni. count.
The bandwidth of the filter and number of channels involved make the
iplexing technique feasible. According to samplim theory, the
giuy rate of sampling a simal to insure recovery of the unsampled
forLatiofl without distortisua is twice the highest sinal frqeuency
in the sampled information. For a3 db bancheid.th of 16.2 cps the
sampling frequency should be at least (2) (16.2) vz 32.4 ePe? A aemP-
ling,, rate of 75.7 cpa will be ervloyed for the multiplexed filter bank.
The poet-detection integration /Unction is being mechanized with
oepaeitor which will act as an ideal integrator except for nealgible
feats of capacitor leadkage. The effectively ideal integrator is
based on use of a detector output stage which functions as a current
3011Z"CO. This technique is feasible since the integrator will be "daved
OX' discharged and clamped after interrogation of the integrator follow-
ing each integration period. The integration time ia 290 milliseconds,
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pad with the iztttilly propoaed 1/3 second.
he piifier of the multiplexed frequence cetectio
ave an AC4 loop to provide 110 db 30 db, of gain
nt
This
1 is reqeired to main nin a constant verage noise
lifter output, The average noise /meat to the f
IP will not be constant bac luso ef the nmeeoryt
t hniques euloyed in the third IF. The control of the AC ar.ierf
Is achieved by use of a reference channel etIch coneists f a wide band-
pass filter multiplexed to the alTlifier end detector utilised by the
40 norasi channels. The detected output of this channel after filter-
ing
w h a Law-pass filter which has a response commensurate with that
pole bane-pass filter, is used as the ACC eignal for the ampli-
The AOC alifier will have an instantaneous ynanic range or
20 db to handle signals &nd noise impulses.
2.7-3 CPiri44.1.10031 TafirxWa
The sequential readout of the post-detection intejratora will be
accomplished with an electronic scanning device. Present plans are
to use a meenetic cure-transistor scanner since this type of aechaniza
tion is met compatible with the ;multiplexed filter bank qtte,
agnetic core scanner particularly satisfies the requirement of isola-
I control signals for bilateral switches employedin the nultiplexing
echome. The news of a recent release, of specifications on a field
erfot transistvr that has a significantly improved saVretedvoltaee
drop characteristic will be investigated within the next reporting
Ultimately this type of device is highly desirable as a re-
placeacnt of chopper transistors lsed as switching elevents, sinee
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on isolated control signal is not required and a microelectronic
scanner then becomes more advantageous.
The interrogation meows will be carried out by the scanner at
a 44.52 kc rate (22.5 usec/itep). Doth left and right banks will be
scanned twice, position for position, so that a relative comparison
nv be Aade of the outputs of corresponding channels. In the first
Interrogating scan of the post-detection integrators decieione are
'ade regarding the presence or absence of a target in the left bank.
The second interrogating scan provides the eame infornation for the
right bank. The decisions about targets are presented to the Data
Pmee
sor unit for further processing.
The samNing of signal information will be mechanised using the
34NO
scanner as used for :interrogation, except that the scanning. rate
1111 be 6.36 ke. This tine-sharing feature reduces overall systen
. The logic and control circuits of the filter bank will be
,lochanized to a large extent with microelectronic circuits.
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A
YSTE PLPN8 FOR I1X RI1DG PliRIO1
t znth great
item specifications
a
d placing firm order*
t for -e first engineering f.dei. Plane for system testing and
orpiment required will be given the fall attention
analysis and integration group this month.
ke of he hardware cheek points we expect to pass are:
layout of all boards for engineering model.
(b) stt layout of model. pallets.
(c) Start building boards for engeering ideIj.
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Approved For Release 2
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3. ANTENNA SUBSYSTEM
3.1 ANALYSIS AND MODEL STUDY
3.1.1 Analysis
A previous section has discussed the trade-offs
obtainable in the symetrical vs. the asymetrical antenna
arrangement. As an independent check,because this work is ,
,
rather tedious and subject to error, .the antenna coverage
was run on a digital computer. The results of the two
approaches are in close agreement, showing that the designed
coverage is obtained more easily with the .5A asymetrical
spacing and the ambiguity problem is greatly minimized.
3.1.2 Model Study -Traveling Wave Antenna
The groundillumination requires two line sources of
about 18 ft. length on the under side of the vehicle. This
can be accomplished with a travelina wave antenna as well as
the discrete resonant slot element antenna that will be dis-
cussed in the following section. As of this time, the choice
has not yet been made as to which of the two will be finally
used. The advantage of the traveling wave antenna is in relative
simplicity-, low weight and possibly in bandwidth, while the
discrete element antenna is more conventional and hence is a
sure approach.
The antenna being developed is a TEM wave excited slot
as in the accompanying figure 3-1. Like the lumped element
model the width is greatly restricted by space available,
making the slots far from resonant. There are 40 slots per
wavelength, which are tightly coupled to the total line
current making it possible: to get a reasonable radiation per
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/
I/ /
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1.1AVVY
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The wave velocity giving a beam as required at 300
from endfire is 115% of free space. This fast wave is
achieved by a .010" out through the ladder between each
sixth gap, providing series capacity in the line. (See
figure 3-1). In general it has been found easier to form
a beam closer to the broadside direction. Thus the problem
reduces to slowing the wave down sufficiently to give the
correct pointing direction, and to simultaneously achieve
high gain and low side lobes. The closest that has been.
realized to this time is about 6 db gain at 34? from end
fire with 10 db side lobes.
3.1.3 Pana tor Next Reportin per Analysis andStudy
Thls radiation is now far enough along that it can be
used to model the complete antenna, both in the 1 and the
1/2 x transverse separation configuration. This will be
done at 4 to 1 scale frequency which is the ratio being used
for the present work. This rather complete model will give
conelusions which are about equally valid for the lumped
element type of antenna and for the traveling wave type of
antenna. A final step in the modeling: work will be to tilt
the slot radiators to compensate for the 18? tilted plane
on which they are mounted.
3.2 DEVELOPMENT OF ELEMENTS AND POWER DIVIDERS
Hardware development and layout for a, full scale
feasibility discrete element demonstration antenna is nearly
complete. This antenna configuration, which consists of an
array of radiating elements fed from power dividers cascaded
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on a single transmission line, is compatible with space
allocation in, the vehicle. Phase control of the radiating
elements will be achieved by the length of coaxial cable
coupling the: radiating element to the power divider.
3.2.1 Radiatin, Elements
A radiatin
ent configuration was developed having
an input impedance equivalent to a single parallel resonant
circuit matched to a 50 ohm line at center frequency with a
3% bandwidth for a VSWR less than 2. This bandwidth may
Increase in array- operation due to the proximity effects of
the other radiators. If a further bandwidth increase is
necessary, it may be achieved by coupling the radiator input
to a resonator through a quarter wave line, producing the
equivalent of a two stage filter.
3.2.2 Power Dividers.
The power dividers being designed are directional
couplers utilizing a pair of enclosed, continuously coupled,
quarter wave long conductors. These power dividers are
located adjacent to the corresponding radiating element and
occupy a one inch square cross-section.
3.2.3 Plans for Next Reporting Periodand Po
5Tifider
The design of radiating elements and power divider
fora full scale demonstration antenna will be completed and
released for fabrication.
3.3 FABRICATION AND TEST OF DELIVERABLE. ANTENNA SYSTEM
No fabrication releases have yet been made in this area.
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